text:
Published: Friday 12th December 2014 by The News Editor
Comedian Russell Brand has condemned Nigel Farage as a "pound shop Enoch Powell" as the pair clashed on television.
Appearing on the BBC's Question Time, the Ukip leader insisted Britain was "overcrowded" and immigration was driving down people's quality of life.
Dismissing a suggestion from an Office for Budget Responsibility (OBR) board member that there is "masses" of room in Britain, Mr Farage said: "If you fly into Gatwick you will see lots of green spaces, that is certainly true.
"However, if you have a country in which the population goes up as a direct result of immigration, what you find is not a shortage of green fields … you find a shortage of primary school place, you find a shortage of GP surgeries."
But Brand hit back by comparing the MEP to Tory politician Powell, who is known for his 1968 "rivers of blood" speech on immigration.
"I sometimes feel worried about you, Nigel Farage … immigrants are not causing the economic problems and suffering we are experiencing," he said .
"As much as any of us I enjoy seeing Nigel Farage in a boozer with a pint and a fag laughing off his latest scandals about breastfeeding or whatever, I enjoy it.
"But this man is not a cartoon character. He ain't Del Boy. He ain't Arthur Daley. He is a pound shop Enoch Powell, and we've got to watch him."
Brand defended his decision not to vote at elections, arguing that politicians had to "give us something to vote for".
The comedian and actor did come under fire for sexist behaviour and bullying fellow panellists.
As communities minister Penny Mordaunt praised firefighters, Brand interrupted, saying: "Pay their pensions then, love. Excuse the sexist language, I'm working on it."
But shadow international development secretary Mary Creagh told him: "One of the things that people really don't like is men talking over women on these types of shows, and our voices not being heard."
Published: Friday 12th December 2014 by The News Editor


text:
AboutHello, my name is Hilda. I'm an aspiring writer, who's started her own book called Phenomenon. If you're curious you can read what I have here, http://www.phenomenonstory.com/
I'm also an artist. Most of my artwork is on deviantArt, as well as some of my writing. http://phenomenons-weaver.deviantart.com/ . On the topic of art, I'm also willing to do commissions so if you like my art and would like something from me you can buy your own personal drawing here, http://fiverr.com/ms_kaellens/draw-what-you-want-in-my-style
Lastly I do have a youtube channel with a few videos. It's on a bit of haitus till I find some time to continue what I've started. If you're interested in taking a look at that as well here's a link. http://www.youtube.com/channel/UCQimTQSXOHIicp24ffKiXIw/feed?activity_view=3
I'll wrap this up with a little bit more about myself. I love playing video games. Recently I've been playing Sims 3 and Elder Scrolls V: Skyrim. Some of my favorites though are the Devil may cry series, Final fantasy 8, 9, and 10.
I also enjoy reading, though I can be a little picky, but I have two authors that have a majority of books I enjoy. The first is Kelley Armstrong, and the second is Christopher Pike. I recently finished the first book of Tamora Pierce's Circle of magic quartet and have started the second book.
I didn't mean to let this get so long. Anyway, feel free to send a message or say hello. : )

subset: commoncrawl


text:
Twitter Refreshes Mobile Apps
Article Comments 1
Apr 3, 2013, 1:59 PM by Eric M. Zeman @phonescooper
updated Apr 3, 2013, 2:26 PM
Twitter today made significant updates available to its Android and iOS apps. On the Android side, the foremost change is the app's partial adoption of the Holo theme. The update makes it easier to perform searches with improved autocomplete for hash tags and usernames. The app also makes some performance improvements. It is a free download from the Google Play Store. Both the iOS and Android apps make it easier to launch other apps from within tweets made using that app. The apps also include better support for Twitter "cards", which enhance tweets with extra media and text related to a web page linked in the tweet. Twitter's mobile web site has also been updated with most of these features.
more info at Google Play Store »
more info at Twitter blog »
Twitter Overhauls Its Mobile Apps and Web Sites
Twitter today revealed a dramatic change to the look and feel of its Android and iOS mobile applications, and its mobile and desktop browser experiences. To start, Twitter has put profile, account, and privacy settings in a single place within the navigation menu to make them easier to find.
Twitter Adds 'Connect' Tab to Help Find Accounts Worth Following
Twitter today announced a new tool meant to make it easier to find new people and accounts to follow. The "connect" tab will appear on Twitter for the web, and in the Android and iOS mobile apps beginning today, where Twitter will curate a list of accounts it believe users might like to follow.
Twitter for Windows 10 Overhauled for Mobile and PCs
Twitter for Microsoft's Windows 10 platform has been given a significant update, putting it more in line with the apps available to Android and iOS devices. For example, Twitter now includes the Moments tab for summaries of current events and support for inserting GIFs into tweets.
Twitter Rolls Out Polling Feature to Android and iOS Apps
Twitter today said anyone will be able to create polls from their mobile device thanks to an update rolling out this week. Twitter says users can create two-choice polls right from the Tweet composition box.
April fools.
Thanks for confusing me guys. Haha.


text:
Puppy: Lilly
Friends: 0
Member Since: April 14, 2013Add to Friends
Hi, I'm Lilly. My new owners just picked me up yesterday and I already love them so much! I enjoy licking and playing with them, and they give me so much love. So far my hobbies are sleeping on my humans' laps, playing with my bone, and prancing around outside in the grass. I am working on being potty trained and am doing such a great job! I can't wait for this summer because my owners tell me they are going to take me everywhere with them including the doggie beach!View Profile


text:
Q&A With Baker Botts' Mary Spearing
Q: What is the most challenging case you have worked on and what made it challenging?
A: I have had several challenging cases as a defense lawyer but...
To view the full article, register now.
Try Law360 FREE for seven days
Already a subscriber? Click here to login


text:
|Publication number
|Publication type
|Application number
|Publication date
|Oct 31, 2006
|Filing date
|Aug 14, 2003
|Priority date
|Aug 22, 2002
|Fee status
|Also published as
|Publication number
|Arie Shahar, Eldan Halberthal
|Original Assignee
|Main Street Ventures, Llc
|Export Citation
|BiBTeX, EndNote, RefMan
|Patent Citations (6), Referenced by (9), Classifications (31), Legal Events (4)
|External Links: USPTO, USPTO Assignment, Espacenet
This application claims the benefit of U.S. Provisional Patent Application Ser. No. 60/405,697, filed Aug. 22, 2002, entitled "Streaming signal control system for digital communications", and of U.S. Provisional Patent Application Ser. No. 60/420,112, filed Oct. 21, 2002, entitled "Streaming signal control system for digital communications".
The invention relates to communications systems and more particularly to the modulation and control of signals for example by interaction of energy in a stateless controller device.
In the field of optical communication, there is a pressing need to improve the capacity of optical networks and the speed of switching at reasonable cost. These are attended by the related problems of efficient retrofit to existing infrastructure, ease of maintenance, reliability, etc. The physical media of optical fibers used in current generation optical networks have a tremendous as yet untapped reserve capacity. The reasons for this involve various bottlenecks, chief among them, the slow speed of switches for optical data. To switch optical data, either the data on an optically-modulated signal must be converted to electrical modulation and switched by electrical switches, switched by relatively slow state change switches such as electro-optical, or thermo-optical switches, or switched by slow mechanical switches like Micro Electro Mechanical Systems (MEMS). Although the electrical conversion and switching is slow it is still much faster than any technology available today for optical switching. The optical switches are too slow to handle information switching and thus are used only for system management and reconfiguration in which the recovery time that may be tolerated for such application is in the range of microseconds to milliseconds. Some of the switches are much faster than the recovery time of the system and some of them have a time response of 50 ns, but still they are too slow for being used for the purpose of data switching fast enough as to avoid storage, which inevitably involves conversion. Electrical switching is the only technology available today that is capable of acting as a switch in the sense of intelligent switching or packet switching, because of the storage capability. While the switching is intelligent, it is still slow and constitutes a major bottleneck in communication networks. To compensate for the slowness of electronic switching, substantial parallelism must be introduced into the design of switches resulting in high cost, large footprint and power consumption. These limitations are near their upper limits making them very difficult to scale.
Currently, there is no all-optical analog to the network switches used in networks.
In addition to the switching process per se, the process of generating optical signals—the modulation itself—is slow because of the rise and fall times of current optical modulators. As a result, symbols are much longer than need be, thereby limiting the bandwidth to a level substantially below the potential of the optical media.
A technique called Wavelength Division Multiplexing (WDM) and a refinement called, Dense Wavelength Division Multiplexing (DWDM) are currently used to increase the capacity of optical media using current modulation technology. WDM or DWDM methods increase the transmission rate by creating parallel information channels, each channel being defined by a different light frequency. Another method, Time Division Multiplexing (TDM) exists in which multiple data sequences are interleaved in time-division fashion on a common medium.
WDM or DWDM methods increase the transmission rate by using parallel information channels. The information in each optical channel is carried by a different light frequency. The light frequencies of the channels are combined together and are inserted into the input of a single optical fiber. The combined light frequencies at the output of the fiber are separated into different parallel channels, one for each specific light frequency. Although DWM and DWDM have the ability to increase the capacity of a fiber, the number of channels that may be defined has a practical upper limit because of the limited bandwidth of the fiber (optical properties are attuned to a narrow range of frequencies) and because of the ability of the laser sources to contain their energy in very narrow frequency bands.
Even if the line-width of the lasers would be made sufficiently narrow to allow the addition of more channels, the number of channels cannot be increased without limit. Increasing the number of channels results in channel crosstalk. Crosstalk results from nonlinear effects that occur within fiber media when subjected to the intense electrical fields produced when a high channel count is used. In TDM, the bits of several parallel channels at the same light frequency are interleaved in a predetermined periodic order to create a single serial data stream. This method is very effective when using a buffer, which accumulates and compresses the data of several channels into a dense serial data stream of a single channel by reorganizing this data with suitable delays. However the data rate permitted by this method, as well as others, is still limited by the data rate and duty cycle of the modulators or the light sources (DFB and DBR lasers) themselves when direct modulation is used. That is, in direct modulation, the power to the laser is switched on and off. The rate at which this can occur has a physical upper limit due to the relatively long recovery time of the lasers and it produces chromatic dispersions due to broadening of the emitted spectral line of the modulated lasers. This is caused by spontaneous emission, jittering, and shifting of the gain curve of the lasers during the current injection. Where modulation is performed in an indirect manner, by modulators, the lasers are operated in a Continuous Wave (CW) mode and separate modulators perform the modulation of the beam. The modulators are usually made from interference devices such as Mach-Zender's, directional couplers and active half wave-plates combined with polarizers and analyzers. However, an electro-optical device must be activated to modulate the beam and thereby produces phase shifts and polarization changes. Such changes involve the creation and removal of space charges, which change the density of the charge carriers within these electro-optic materials. The formation rate of the space charges is mainly dependent upon the speed and the magnitude of the applied voltage and can be on the order of sub nanoseconds. The charge removal is usually slower and is mainly dependent upon the relaxation time of these materials (lifetime of charge carriers) and can be relatively long. Accordingly, the width of the pulses and the duty cycle of the modulation are dependent limited by the long off-time (latency) of the modulators.
These same rise and fall time limitations impose similar limits on the abilities of switches to direct light along alternative pathways according to routing commands and data. At present, there are two major classes of optical switches. In one class, optical signals are converted to electrical signals, routed and switched conventionally, and optical signals generated anew at the output. As discussed above, the process of conversion is costly and the reduction of switching time is limited since the switching time includes delays due to reading, processing of destinations, reconfiguration delays, device I/O, and regeneration of the optical signals. Thus the switching time is slow requiring many parallel channels to obtain throughput making such switches scale poorly, costly, and otherwise problematic. In optical applications, this class of switches goes by the identifier OEO, which stands for signals medium conversion, from the optical domain to the electrical domain and then back to the optical.
A second class of optical switch, which is often very slow to reconfigure, goes by the identifier OO, which stands for optical-optical, as the signals are maintained thoroughly in the optical domain. In these switches, no conversion of optical signals to electrical signals takes place. Instead, the optical energy is routed by means of some sort of light diversion process such as a switchable mirror. In one system, micromechanical actuators or so-called Micro Electro Mechanical System (MEMS), use electrostatic forces to mechanically move microscopic mirrors in response to electrical routing signals. The speed of such switches is very limited by the slow response of the devices used to perform switching, for example, MEMS mechanism. The result is that no OO switch is capable of packet switching and is only applicable where the granularity of data signals is extremely high, such that the delays required for configuration represent a small fraction of the time required for transmitting. These devices are applicable in the core portions of networks and do not address the bottleneck problems inherent electronic switches.
At present, the highest bit rate being deployed is about 10G bits per second per channel. Higher bit rates designs, such as 40G bit per second per channel, are mainly challenged by developing high bit rate devices, improve optical signal-to-noise ratio and compensate for dispersion. Present high speed 10G bits per second devices are limited by the modulation rate of the modulators, the pulse width that they produce, and the switching time of the electronic switches.
There is a need for reliable mechanisms for exploiting the physical potential of fiber optic media in terms of data rate, switching, and cost.
In optical communication networks there is a need for fast, reliable, and inexpensive systems capable of demultiplexing information. One solution for such a need is provided by Passive Optical Networks (PON) that passively demultiplex the information, by splitters, into multiple customers. Such PON systems have a common use in applications for the last-mile. However such a solution suffers from security problems since every attached PON network customers receives the whole information of all other network customers, regardless of the targeted customer. Accordingly it is desired to produce an inexpensive, simple demultiplexing system in which each customer receives the information in a direct manner and only the information designated specifically to him.
U.S. Pat. No. 5,060,305 entitled "Self Clocked, Self Routed Photonic Switch" filed Oct. 22, 1991 and U.S. Pat. No. 6,160,652 entitled "Optical Address Decoder" filed Dec. 12, 2000, disclose systems and devices for decoding headers in an architecture of sending information by payloads where the destinations of the payloads are encoded in the headers.
The design of the embodiments according to the present invention allows simple direct demultiplexing of the information without the use of headers and payloads. Thus the embodiments of the present invention are simpler, more reliable, faster, and less expensive than the embodiments disclosed by U.S. Pat. Nos. 5,060,305 and 6,160,652.
Accordingly, it is an object of the present invention to provide a passive, inexpensive, and reliable system for direct switching, routing, multiplexing and demultiplexing of information;
Another object of the present invention is to provide passive and fast systems for direct switching, routing, multiplexing and demultiplexing of information in which each customer may receives information directed only to him;
Another object of the present invention is to provide a fast system for direct switching, routing, multiplexing and demultiplexing of information that may include a threshold mechanism and switch the information in a direct manner;
Another object of the present invention is to provide a fast system for direct switching, routing, multiplexing and demultiplexing of information across multiple decoding/switching/routing/demultiplexing layers;
Another object of the present invention is to provide a fast system for direct switching, routing, multiplexing and demultiplexing of information to form cross connection switching and cross-connection boxes for decoding/switching/routing/demultiplexing of information;
Another object of the present invention is to provide a fast system for direct switching, routing, multiplexing and demultiplexing of information that may include a threshold mechanism and in which each customer receives information directed only to him;
Another object of the present invention is to provide fast systems for direct switching, routing, multiplexing and demultiplexing of information including coincidence gates or decoding devices that may be stateless;
Another object of the present invention is to provide coincidence gates that include a summing gate that may be of one of the type of dielectric and metallic beam-splitters, dual gratings, high density gratings, array of radiation guide gratings, Array of Waveguide Gratings (AWG), polarization beam-splitters, directional couplers, and Y-junctions;
Another object of the present invention is to provide coincidence gates that may be produced in any of the media including, open space, radiation guides, fiber optics, wave guides, and planar wave guides fabricated on a chip;
Another object of the present invention is to provide coincidence gates including summing gates that may sum the control and the data signal coherently or non-coherently;
Another object of the present invention is to provide coincidence gates including summing gates that may sum the control and the data signal coherently and have closed loop phase control;
Another object of the present invention is to provide coincidence gates including electrical or optical threshold mechanisms;
Another object of the present invention is to provide coincidence gates that may receive in their inputs control and data signal for a single source or from different sources;
Another object of the present invention is to provide coincidence gates including summing gates that may sum the control and the data signal and have closed loop clock recovery control;
Another object of the present invention is to provide a method and apparatuses to increase the rate of information transmitted using narrow pulse generators and shapers and dense interleaving to produce high dense multiplexing and demultiplexing;
Another object of the present invention is to provide codes with predetermined destinations including at least one control pulse and one data pulse;
Another object of the present invention is to provide codes with predetermined destinations including multiple control pulses;
Another object of the present invention is to provide codes constructed from a plurality of pulses with predetermined destinations including multiple control pulses to route, switch or demultiplex information across multiple routing, switching and demultiplexing layers;
Another object of the present invention is to provide symbol configurations, summing gates, and control pulses for increasing the ratio between coincidence pulses and non-coincidence pulses produced by coincidence gates;
Another object of the present invention is to provide coincidence gates including delay lines;
Another object of the present invention is to provide coincidence gates including variable delay lines;
Another object of the present invention is to provide coincidence gates including delay lines compactly produced on a chip;
Another object of the present invention is to provide optical cross-connection boxes capable of information self routing;
Another object of the present invention is to provide a self routing, switching and demultiplexing mechanism that maintains synchronization;
Another object of the present invention is to provide a self routing, switching and demultiplexing mechanism across DWDM systems that may include multiple switching layers;
Another object of the present invention is to provide embodiments designed to multiplex/demultiplex symbols with predetermined addresses including management of guard band between symbols, and,
Still another object of the present invention is to provide embodiments designed to multiplex/demultiplex symbols with predetermined addresses modulated by any combination of time, phase, and polarization modulation.
An all-optical system for modulating, switching, multiplexing, demultiplexing, and routing signals, for example digital signals in an optical medium, employs control units that direct energy according to a coincident control signal which may be in the same form as the digital signal. Briefly, in an embodiment where the signals are optical, any of a variety of different interactions between light inputs results in a combined output with a different magnitude when both inputs coincide than when they do not. For example, an energy summer produces an output whose power is proportional to the sum of the two inputs when the two inputs coincide and whose power is proportional to the individual inputs when the two inputs do not coincide. In an example embodiment, a control signal determines the power level of the output based on some addressing technique by combining the control signal at one input with a data signal at the other input. The control and the data signals may arrive from the same source of from different sources. The resulting signal has a higher magnitude when control and data signals are combined than when not. The output may be received by an optical-electrical transducer (e.g., a photodiode circuit) or an all optical threshold device configured to discriminate signals above a predefined threshold (electronically or optically) from signals below the predefined threshold. In such a receiver, data signals that are summed with a control signal are accepted as received data, while signals that are not summed (and, as a result, having a power magnitude below the threshold) are rejected. In an application of this example using a summer, a transmitter modulates a light beam to form pulses, each representing a bit consisting of a data pulse and a control pulse whose spacing represents a destination address. The modulated beam is applied in parallel to a set of summers. Each summer has a non-delayed input and a delayed input (or two inputs when each input has a different delay). Each summer has a respective delay at its delayed inputs (or between its inputs) such that a given spacing between the data and control pulses causes a coincidence at only one of the summers. The outputs of all the summers are sent to respective receivers, each configured to reject signals whose magnitude is below a specified threshold. Only one receiver will accept the data pulses "addressed" for the gate (i.e. whose spacing corresponds to that gate's control input's delay) connected to that receiver. In this embodiment, pulse-pairs will produce a single output pulse whose magnitude meets a threshold only at a single receiver. This function results in, effectively, a routing of each data bit to a selected receiver over a channel connected to multiple receivers.
In the above example, a simple summer can be fabricated from a Y-junction, directional coupler or a beam splitter, all commonly used in optical communications circuits. For example, it can also be fabricated from other optical devices used for energy summing, such as, transmitting and reflecting grating, fiber grating or other coupling devices. The light energy is preferably formed of light of a range of propagation modes, frequencies, phases or any combination between them, so that the signal power summing effect is produced non-coherently. Alternatively, the light at one input can be a different frequency than the light at the other input with the gate output being a mixture of the two input frequencies.
In further embodiments, the gate directs a substantial fraction of the energy pulses (including symbols) in a data signal to a first output when light from its two inputs are coincident, in its summing region, and to a second output when there is no coincidence. This effect can be produced by coherent summing, for example by means of a beam-splitter or directional coupler. In these embodiments, the interaction is coherent resulting in interference between the light signals applied at the two inputs. The power of the output when the input energy is coincident, in these latter embodiments, may be greater than the sum of the energy produced at the outputs in non coincidence situations. Several variations on these embodiments are described:
In one embodiment, the E-fields of the two input signals are summed providing an output whose power is up to four times the power of either output when one input alone provides a signal (assuming the two inputs have the same power level);
In another embodiment, the E-fields of the two input signals are summed. The resultant output is added to a signal generated by a separate source whose E-field magnitude is some fraction of that of the output resulting from coincidence of the inputs and out of phase with it such that the magnitude ratio of the signal at the coincidence output in a coincidence state to the signal in a non-coincidence state is increased. For example, if the E-field of the constant source is one half the magnitude of the non-coincidence signal at the coincidence output and out of phase with it, the energy magnitude of the signal in a coincidence state at the coincidence output will be nine times the magnitude of the non-coincidence signal at that output.
In a further embodiment, the pulses may be formed such that there is a negative E-field added to them, whose amplitude is, for example, a third of the E-field of the pulses and 180 degrees out of phase. Then, when the pulses are added coherently, the coincidence pulse power level is up to nine times (for the −⅓, +1 example) greater than that of the level of the non-coincidence pulses or the "floor" level between the pulses. In an additional embodiment, pulses with E-fields having different polarizations may be summed to generate, by vector addition, a pulse with a different polarization angle matching that of a polarization filter such that the energy of either component is substantially more attenuated than that of the sum. The ratio between the output energies of the signals in a non-coincidence state and a coincidence state, at the coincidence output, is depend on whether polarization filter is used or not in the output(s) of the control device. It also depends on the relative polarization orientation between the inputs beams. When pulses, whose E-fields at respective inputs are in phase, but with a difference in polarization angle of π/2, are summed by a polarizing beam splitter, the above ratio at the output is 4:1 when a polarization filter is used at the output and 2:1 when such a filter is not used. This ratio can be increased to 9:1 by adding CW field, with the appropriate magnitude phase and polarization, to each of the inputs or to the summed outputs. It is also possible to select one of two outputs providing the coincidence behavior by changing the phase of one of the inputs relative to the other.
Other control mechanisms may be employed besides the addressing scheme mentioned above. For example, a pulse sequence could be compared in a gate, such as described above, to a predefined pulse sequence defining an address. The gate may be configured such that if the addresses match, high-level signals are output due to consistent in the gate. Alternatively, the gate may be configured such that if the addresses match, only low-level signals are output due to non-coincidence in the gate. Other modulation schemes could also be used in connection with the present invention, for example, phase modulation, polarization modulation or any combination of them.
Phase modulation is produced by the relative phase between the data and control signals. When a control signal and a data signal are coincident with equal phases, at respective inputs of a control unit, most of the data signal energy is directed to one output (the coincidence output for phase matching). Alternatively, when a control signal and a data signal are coincident with opposite phases, at the same respective inputs of a control unit, most of the data signal energy is directed to the other output (the coincidence output for anti-phase). Accordingly, the appearance of a high-energy signal in one of the outputs of the control unit depends on the coincidence and the phase conditions.
Polarization modulation is produced by the relative polarization between the data and control signals. When a control signal and a data signal are coherent and polarized along the same direction, at respective inputs of a control unit (even if the control unit is polarization-insensitive), most of the data signal energy is directed to one output: the coincidence output corresponding to phase matching. Alternatively, when the control unit is polarization-sensitive and receives, at its respective inputs, control and data signals that are polarized along directions that are normal to each other, most of the data signal energy is directed to one of the outputs of the control unit. The coincidence output can be selected by the relative polarization orientation and phase between the energy at the inputs of the control unit. Accordingly, the appearance of a high-energy signal in one of the outputs of the control unit depends on the coincidence, the phase, and the polarization conditions.
Combined modulation can be achieved by any combination of the modulation methods, i.e., time, phase, and polarization. A combination of modulation methods increases the number of independent parameters that each symbol contains and thus increases the amount of information that each symbol can carry.
When a control signal and a data signal are coincident at respective inputs of a control unit, most of the data signal energy is directed to one output and when the control signal is non-coincident with the data signal, most of the data signal energy is directed to another output or simply discarded. According to an embodiment, this "coincidence-gate" behavior is brought about by the interference of the control and data signals. Note that reference to one signal as a control signal and the other signal as a data signal is, at least in many embodiments, an arbitrary choice and may be used in the present specification simply to facilitate the description of the invention. The described addressing technique may include signals having multiple control pulses. The multiple control pulses are constructed such that they can only be decoded by a single combination of multiple coincidence gates. Such a technique may also be used for addressing across multiple layers of switching, demultiplexing or routing layers.
In an embodiment, the interference of light in the control and data signals is the result of applying one signal to a first diffraction grating that generates a first interference order diffraction pattern and the other signal to a diffraction pattern adjacent or interleaved with the first such that a different interference order is generated when both signals coincide on both gratings. In an example, the first grating may be a transmission grating with (broken or patterned) reflective surfaces between the transmission apertures defining a reflection grating. With such a device, one signal may reflect off of the reflective grating and the other signal may pass through the transmission grating. The reflection and transmission diffraction patterns of either signal produces first order diffracted radiation when only one signal falls on the device at given instant of time. But when both fall on the device at the same time, so that the effective pitch of the diffraction grating includes both the transmission and reflection grating, a lower order diffracted radiation results. In the case of the first order pattern, the number of lobes is higher and they have different intensities from that of the lower order diffraction pattern. With suitably spatially-located receivers, the energy may be directed in different directions from this type of interference device depending on the relative phase between the beams and whether the two signals are coincident or non-coincident. The coincidence gate may thus have a coincidence output to which higher energy is sent when the both inputs receive energy at the same time and a non-coincidence output to which energy is sent when the inputs receive energy at different times. Note, as should be clear to a person of ordinary skill, for the above interference type of coincidence gate to work properly, the phases of the inputs should be properly aligned to insure the energy from the gratings falls on the respective receivers. It should be understood that selecting certain outputs as coincident and non-coincident output may change and each output may serve both, a coincidence and non-coincidence output, depending on the specific application used.
An alternative device for producing a coincidence effect is to perform non-coherent summing. Laser light from a multimode laser or a Light Emitting Diode (LED) characterized by a distribution of wavelengths and/or phases can be modulated and summed non-coherently. In such an embodiment, the ratio of energies of the coincidence output and the non-coincidence outputs may not be as high as with coherent summing, but the effect is still strong enough to be usable for gating.
Using such interference devices, by suitable construction of an optical device, incident energy is directed along different paths depending on whether the data and control beams are coincident on the inputs of the device or non-coincident. The result is a basic component, mentioned above, called a coincidence gate. This gate may be used to control the path of a data signal. For example, by articulating a single data signal so that it contains pairs of pulses separated by a predefined spacing, and splitting this signal, sending one to one input of the coincidence gate and sending a delayed version to the other input of the coincidence gate, the signal will transmit a pulse of higher intensity at an output of a coincidence gate where the pulse spacing matches the delay than at the output of a coincidence gate where the pulse spacing is different from the delay. By sending such a spaced-pulse symbol to a number of different coincidence gates in parallel, each with a different delay, the articulated signal will, in effect, select an output according to the delay matching the spacing of the pulses in the signal. Thus, the optical signal carries a symbol (the pulse spacing) that selects which coincidence gate-device most of its energy will be sent through. This effect amounts to a basic switching function.
Note that the switching function can be layered by providing each output to another set of different gates each with another different delay. To articulate the signal for successive layers, the signal construction may be repeated in self-similar steps for every switch layer involved because each pulse pair only produces a single pulse at the output. The details of this process are described in the Detailed Description section along with supporting illustrations.
The coincidence device may also be used to create a modulator for dense signal transmission because of its rapid on-off response. That is, if two broad pulses are applied to the control and data inputs of a coincidence device with different time delays, the width of the pulse emerging from the coincidence output will be determined by the period during which both input pulses are incident on a gate. Thus, the coincidence effect can be used to generate pulses that are very narrow. Other devices are also discussed for forming narrow pulses. By combining multiple streams from such sources of narrow pulses into a common optical channel with respective delays, very dense streams of narrow pulses may be generated thereby increasing the bandwidth of an optical signal. A mirror-image process can then be used to demultiplex the dense data stream into respective channels with larger pulse spacing at a receiving end. Thus, the above description embodies a multiplexer/demultiplexer combination. Another way of forming dense pulse streams is to modulate multiple parallel channels fed by a mode locked laser and interleaving the pulses.
There are a number of alternative interference devices that may be used to create a coincidence gate. Y-junctions, directional couplers, fast-pitch diffraction gratings, beam splitters, and other examples discussed in the present specification may be used to form coincidence gates and produce a similar coincidence function. These examples are described in the Detailed Description section below along with supporting illustrations.
Also, in addition to the modulation and self-switching functions described above, the coincidence gate may be used as the basis for a switch controlled by an external control signal. Thus, a data signal from one source can be directed to an appropriate output of a layer of coincidence gates by sending an appropriately-timed control pulse to all of the gates. Alternatively, a single selected coincidence gate can have one of its outputs selected by an external control signal by transmitting a control signal to only the selected coincidence gate.
An additional layer of symbology may be added to an optical signal which may be used for switching purposes in coincidence gates employing the diffraction phenomenon. The propagation directions of the various diffraction orders may be varied by imposing different phase relationships between the data and control signals. By placing receivers in different locations, each set with different outputs, the coincidence gate may be configured to provide selectable outputs depending on the phase relationship between the pulses.
The present invention provides an optical system for decoding, switching, demultiplexing, and routing of optical encoded data symbols, including:
a plurality of optical paths having first and second terminals;
a splitting mechanism for directing the encoded data symbols to each of the first terminals;
a plurality of decoding devices for producing decoded signals in response to the encoded data symbols; and
each of the optical paths includes, between the first and second terminals, at least one of the decoding devices to produce one of the decoded signals at one of the second terminals in response to one of the encoded data symbols.
The present invention also provides an optical system for decoding, switching, demultiplexing, and routing of optical encoded data symbols, including:
a plurality of radiation guides having first and second terminals;
a splitting mechanism for directing the encoded data symbols to each of the first terminals;
a plurality of decoding devices, each of the decoding devices produces one of a plurality of decoded signals in response to one of the encoded data symbols; and
each of the radiation guides includes, between the first and second terminals, at least one of the decoding devices to produce one of the plurality of decoded signals at one of the second terminals in response to one of the encoded data symbols.
In another version, the present invention also provides an optical system for decoding, switching, demultiplexing, and routing of optical encoded data symbols, including:
a first plurality of radiation guides having first and second terminals;
a first splitting mechanism for directing the encoded data symbols to each of the first terminals of the radiation guides of the first plurality of radiation guides;
a plurality of decoding devices each of the decoding devices includes a second plurality of radiation guides, each of the radiation guides of the second plurality of radiation guides associated with one of the ports of a second splitting mechanism and with one of the ports of a combining mechanism, the decoding devices are arranged for producing decoded signals in response to the encoded data symbols; and
each of the optical paths includes, between the first and second terminals, at least one of the decoding devices to produce one of the decoded signals at one of the second terminals in response to one of the encoded data symbols.
While some of the embodiments of the invention are illustrated as being constructed in one of the media of open space, fiber optics, radiation guides, waveguides, and planar waveguides on a chip, each of them may be fabricated in any of these media. It also should be clear that while the descriptions below describe coincidence gates they are also decoding devices. While the optical encoded data symbols may also be described, below, as encoded signals, signals including information and control pulses, symbols, symbol signals, spaced-pulse symbols, pulse patterns and signals, it should be clear that they all may represent optical encoded data symbols as well as other signals defined by other terms that may describe equivalents to optical encoded data symbols.
The invention will be described in connection with certain preferred embodiments, with reference to the following illustrative figures so that it may be more fully understood. With reference to the figures, it is stressed that the particulars shown are by way of example and for purposes of illustrative discussion of the preferred embodiments of the present invention only, and are presented in the cause of providing what is believed to be the most useful and readily understood description of the principles and conceptual aspects of the invention. In this regard, no attempt is made to show structural details of the invention in more detail than is necessary for a fundamental understanding of the invention, the description taken with the drawings making apparent to those skilled in the art how the several forms of the invention may be embodied in practice.
The invention is herein described, by way of example only, with reference to accompanying drawings, wherein:
Referring to
Referring now to
By providing an appropriate detector, such as, detector 90, to the gate 100, it can be determined whether a signal was applied to either input 5 or 10 independently or to both in a certain temporal relationship. This may be determined by detecting the presence of a pulse 72 versus either pulse 70 or 71, for example, by comparing an intensity level of the respective pulses. Thus, for example, if a receiver is configured to detect only pulses of the form 72, a signal modulated to carry data and applied at one of the inputs 5 or 10 may be detected as such at the output 15 only when a "control signal" is applied at the other input 10 or 5 simultaneously and respectively. In this case, for example, a data signal at input 5 may be considered to be passed or blocked depending on the coincidence of a signal at input 10. Thus, one of the inputs can be regarded as a control input and the other as a data input. In
Referring to
It is assumed that the energy incident on the dielectric beam splitter 110 consists, at least substantially, of a single wavelength of light, although, as discussed below, in further embodiments, they consist of non-coherent radiation such as multiple wavelengths, propagation modes, phases or any combination of them. Where the light signals are non-coherent, the power combination effect is correspondingly different with simple power summing, rather than field summing, taking place.
Referring to
Note that the output may be taken as 145, 165 or 150, 170 as well and still fall within the description of the gate 100, depending on the interpretation of the received signal, the relative phase between input beams 115 and 160, and how data is represented. When using coherent energy, such as light, the energy ratio between the energy of the coincidence pulse, at the coincidence output, and the energy of the non-coincidence pulse at that output is up to four. When using non-coherent light this ratio is up to two. The differences between the above ratios is due to the fact that when using coherent light the control device (gate 100) acts as a field combiner while it acts as a power combiner when using non-coherent light. In addition, when using coherent radiation, the coincidence signal is produced at only one output and the non-coincidence signal is null. Thus the energy that is divided between two outputs, in a non-coincidence situation, is emitted from only one output, in a coincidence situation.
Note that if the phase of either input signal 175 or 180 is changed by π, the coincidence output pulse will emanate from the port 113 rather than the port 112. This effect may be used to "direct" the coincidence pulse 190 based on a phase encoding of one or both of the input signals. As will be discussed below, this along with the selective gating effect may be used to perform a communications function as performed by a switch or multiplexer/demultiplexer.
Referring to
Referring to
Referring now to
Referring to
Referring to
The intensity of the lobes in interference patterns 301, 303, 319, 321, 327 and 329 are schematically illustrated and do not represent the actual relative intensity of the lobes where, actually, the side lobes are smaller than the central lobe. The transmitting gaps 313D and the reflecting elements of surface 313A can be broadened to convert grating 310 into transmitting and reflecting binary grating. In such a case the side lobes has half of the intensity of the central lobe.
When using coherent light the energy ratio between the energy of the coincidence pulse, at the coincidence output, and the energy of the non-coincidence pulse at that output is up to four as a result of the reduction of the number of lobes due to field interference. When using non-coherent light the number of lobes in the interference pattern does not change and the above ratio is up to two as may be predicted since the energies are summed.
Referring now to
Referring to
Referring to
Note that the port from which the coincidence pulse emerges 377 or 379 can be selected based on the phase relationship of the input signals 361 and 363. As in the embodiments of
Referring to
Referring to
Referring now also to
Referring now to
Further polarization filters 425 and 426, with respective orientations 425A and 426A, may be used to enhance the difference between coincidence and non-coincidence outputs. That is, the outputs 428E and 428D may be further filtered by polarization filters 425 and 426 to produce outputs 424A and 424B. Two input ports I1 and I2 and two output ports O1 and O2 are defined as illustrated. As discussed below, one of the two output ports Ol and O2 may be used alone as a selecting blocking gate or in combination so that the polarization device can be used as an output switch. In
Referring now to
The output 428A, according to a further embodiment, may be filtered by polarization filter 425 with the polarization orientation indicated. The latter, as shown, forms an approximately π/4 angle with the orientation of the polarization filter 425 so that the output signal 428A is attenuated accordingly, causing the magnitude of the output E-field 424A to be √{square root over (2)}/2 and its orientation to be aligned with that of the filter 425 as indicated at 422A.
Referring now to
As in the embodiments of
Referring now to
As in the embodiments of
As should be clear from the above discussion, an output 424C is obtained, when inputs 419A and 419B are coincident, whose intensity magnitude is four times that of the output 424A or 424B when either input 419A or 419B is incident by itself. This behavior is similar to embodiments previously discussed. If light having multiple frequencies or phases (or multimode light) is used, the polarization device 418 acts as a simple power summer rather than a field summer. Thus, the power of the output will not be as great as when coherent light, suitable phase-aligned, is used. As should also be clear from the properties of the polarization filter device 418, if the polarization angles of the inputs 419A and 419B are rotated by π/2 (in either direction), similar results will be obtained as above, except that instead of the outputs 428A, 428B and 428C being generated at output O1, they will be generated at O2, such as illustrated by output 428D of
Using the configuration of
The directional coupler device 443 may also be used as a gate device conforming to the description for gate 100, as discussed with reference to Table 1, below.
Field magnitudes of inputs and outputs
for directional coupler-based gate
When the indicated inputs I1 and I2 are applied in combination in a given row, the corresponding outputs O1 and O2 are given in the same row result. The phase relationships are relative and depend on the precise structure and materials of the directional coupler device 443, which determine delays, coupling length, etc. As will be clear to those of skill in the relevant fields, a structure may be created to provide the above behavior or a simile. As should be immediately clear, the ratio of power at output port O1 when the input signals are coincident is four times that when one signal arrives at a time, as indicated in Table 1. Also, if the phases of the inputs are rotated by π/2, as indicated in the last three rows, the large coincidence output is generated at port O2 instead of port O1. When non-coherent radiation is used, both outputs O1 and O2 produce output signals, even when both inputs applied simultaneously, resulting in a coincidence output signal that its intensity is only up to twice the intensity when only one input is applied alone.
In general it should be understood that for all the embodiments described above (2A–2C, 3A–3C, 5A–5C, 4A–4E, 6A–6C, 7A–7B and 8A–8E) in accordance to
Accordingly, it can be seen that the above described summing gates, which are all represented by gate 100 of
Thus the input state (coincidence or non-coincidence state) of gates 100 can be detected at their outputs by monitoring their output signal using detectors such as detectors 90 and 95 of
Alternatively, the input state of gates 100 can be detected at their outputs using threshold devices. The lower and the higher level signals at the outputs of gates 100, corresponding to non-coincidence and coincidence states at the inputs of gate 100, can be adjusted to be below and above the threshold level of a threshold device into which these signals are fed in order to detect the input states.
The use of a threshold device that follows the summing gate produces an AND logic gate that its output is in logic states "1" or zero when its inputs are in coincidence or non-coincidence states, respectively. The AND gate includes two major units, a summing gate (such as the summing gates 100 described above) and a threshold device (such as described below). The combination of summing gates with threshold devices to produce AND gates, is described, in details, below.
Referring now to
Referring now also to
Further below it will describe in more detail how a variety of communications systems may be configured around the effect described with respect to
By applying the signal 450, via splitters 453A, 453B and 453C to two gates 455A and 455B, each with a different delay device 468 and 469, pulses of magnitude 472 ("coincidence pulses") will be output in output signals 460A or 460B only if the corresponding time delay Δt1 or Δt2 of respective time delay device 468 or 469 of gate 455A or 455B matches the delay between the pulses 450A and 450B. Thus, coincidence pulses will only be transmitted to the receiver 465A and 465B whose corresponding time delay device 468 and 469 matches the delay between the pulses 450A and 450B. If receivers 465A and 465B are configured to be unresponsive to signal levels of magnitude below a predefined threshold that is above that of non-coincidence pulses 466 of
Any number of gates 100 may be added in parallel to the configuration of
Referring now to
Referring to
Referring to
Referring now to
Referring again to
Referring again to
Input signal 503 also does not have a zero level. The field amplitude of the pulse is in opposite phase relative to the field amplitude of the background level and is three times higher. Input signal 503, which may be applied as signal 160 (in
Note that there are only four distinct field sums that arise in the above context:
In situation 1, at time slot t1, for example, where two background levels line up, the resulting magnitude and phase of the signal output at 197 of
and the energy is 2/9.
In situation 2, at time slot t3, adding the pulse 499 in slot t3 to the time and phase shifted background level signal 503 in the same way gives a field magnitude of:
and the corresponding energy is 2/9.
In situation 3, at time slot t5, a pulse 511 is generated with a magnitude that is:
and the corresponding energy of the coincidence signal at the coincidence output is 2.
In situation 4, at time slot t7, the field amplitude is derived in a similar way to given:
and the corresponded energy is 2/9.
It can be seen that only situation 3 produces a coincidence signal with intensity of 2. All the other situations are related to the background level and are with equal intensity of 2/9. This means that the background is flat and that the energy of the coincidence pulse is nine times the intensity level of the background.
The output 507B from the non-coincidence output has a zero magnitude at all points except in time slots t3 and t7, where the intensity magnitude of pulse portions 513A and 509A, respectively, is 8/9 and the pulse field magnitudes are
respectively. Note that if the time shift of signal 503 is not such that any pulses line up, the resulting signal from the coincidence output and the non-coincidence output will have a flat intensity magnitude of 2/9 and serial of four pulses with intensity magnitude of 8/9, respectively. It can be seen that in any situation the sum of the energies at the outputs is equal to the sum of the energies in the inputs.
The advantage of a 9:1 ratio in magnitude between pulse signal 511 corresponding to pulse portion 509 at output 507A (at time slot t5) and background level 512, constructed by artifact pulses, such as, signal portion 513 in time slot t3 of output 507A should be clear from the foregoing where a gate exhibiting these properties is used as a mechanism for switching such as discussed with reference to
Referring now to
Referring specifically to
The field amplitudes of the coincidence pulse and the non-coincidence pulses are 2 and 1, respectively. The signal has a zero background level. After subtracting the CW field that has magnitude of �, the fields magnitudes of the coincidence pulse, the non-coincidence pulses, and the background level are 1.5, 0.5 and −0.5, with their corresponding intensities of 2.25, 0.25 and 0.25, respectively.
It can be seen that all the possible situations, excluding coincidence, are characterized by a power level of 0.25, which creates a flat background level. The coincidence pulse has an energy of 2.25 which is nine times higher than the energy of the background level.
Note that although in the embodiments discussed above the signals added were derived from a common source, it is clear that they may be generated from independent sources. For example, a data signal applied at one port of a gate such as gate 100 could be switched by a locally-generated control signal applied at the other port. In such a case, it may be necessary to provide timing and phase recovery (Phase Lock Loop (PLL)), topics that are discussed in more detail below to provide the above result.
Referring now to
The functionality of the embodiment of
As discussed with respect to signal 533 of the embodiment of
Referring now to
Referring now to
Signal 633, propagating through path 627 is amplified, by amplifier 615 in the linear region to produce a higher-level signal 635 with additional phase shift of π/2 radians. Signal 635 is then attenuated, by attenuator 617 to produce signal 637. The phase of signal 637 is coherently shifted by π/2 radians out of phase with respect to signal 631, at the input of combiner 621. Signal 637 is then added, with opposite relative phases, to signal 631, by combiner 621, resulting in a zero level output 639. The phase shift of π/2 radians between beams 629 and 623, causes subtraction when the combiner 621 is a directional coupler. For a y-junction-based combiner 621 the phase difference should be π radians.
When a signal 647 containing a coincidence pulse and artifact passes through the configuration of
The configuration of
To assure that the coincidence signal 647 of
It should be understood that the cancellator of artifact pulses (or optical threshold device) 690 of
Referring to
An attenuation 582C may or may not be used to attenuate the energy received from amplifier 582B depending on design characteristics of the circuit. Combining, in coupler 582E, only a fraction of the energy received from amplifier 582B is equivalent to attenuating this energy prior to its entrance to coupler 582E. For example, a combiner 582E may couple a chosen fraction of energy from the output signal of amplifier 582B into port 582D so that a corresponding amount, or no, attenuation may be required. The amplified signal and original signal are combined by a combiner 582E to generate an output.
The result of using the amplifier 582B is illustrated in
The amplifier 615 of
Note that the amplifier 582B may also be replaced by a material or NLE whose properties are such as to produce a phase shift that is proportional to the intensity. The latter may include an amplifier as part of the combined structure. For example, such a nonlinear property may be employed by choosing a material and signal level such that the high energy level of the coincidence pulses, produce refractive-index change that will be resulted in a phase inversion relative to the artifact pulses having lower intensity level.
From the observation of the transmission-function shown in
Referring now to
It should be understood that detectors 993A and 993B and comparator (differential amplifier) 990 may be located in close vicinity to coincidence gate 993 to form a logical AND gate. However, detectors 993A and 993B and comparator 990 may be part of a customers' end unit, connected to an optical communication network where the network includes coincidence gates 993. In such a case detectors 993A and 993B and comparator 990 may be located far away from coincidence gate 993 and may be separated from gate 993 by multiple switching layers.
Referring now to
Referring to
It may be observed by inspection that suitable delays need to be incorporated after each symbol including its enhancement pulse to prevent inter-symbol interference. This may be necessary also to prevent undesired interaction in other gates used in the same system (not shown). The precise length of the required guard band will depend on the modulation scheme employed.
Note that junctions 1129A and 1129B may be combined into a single star junction and gates 1125 and 1126 can be implemented as a single combiner, the particulars of the embodiment of
Each branch 1124 (typ.) in the device of
It should be clear that the symbols that include multiple enhancement pulses may be used as multiple control pulses. In such a case the address (destination) of the symbol is determined by the specific time spaces between the multiple control pulses and the data pulse in the symbol. The enhanced coincidence pulse, discussed above, is in this case a main coincidence pulse, produced by a specific combined gate that responds to this specific symbol.
The combined coincidence gate may be constructed from parallel multiple gates, each responding to a different time space between the pulses of the symbol. Each parallel coincidence gate that constructs the combined gate, may be identified by any number, greater than two, of delay branches 1124 (typ.) of
Referring to
Signal 3040 of
Referring momentarily to
Each pulse 3042 of time frames 3046 has double duty to serve both, as a reference pulse for the currently demultiplexed time frame 3046 and as a control pulse for the next following time frame 3046. Signal 3040 propagates in the direction shown by arrow 3048 thus, delayed pulses 3042A and leading pulses 3042B (ahead in time) may serve as the reference and the control pulses for the currently demultiplexed time frame 3046, respectively. Pulses 3042A may also serve as the reference pulses for the leading information pulses 3044 to create data symbols formed by the time delays Δt1–Δtn between pulses 3044 and 3042A. Delays Δt1–Δtn are equal to the delays of coincidence gates 3012A–3012N in combined coincidence gates 3024A–3024N, respectively. The time delay ΔtF between pulses 3042A and 3042B of frames 3046 is equal to the time delay of gates 3014A–3014N of combined gates 3024A–3024N, respectively. All frames 3046 are closely packed and do not include time guard bands between them.
Referring now back to combined gate 3024A of system 3000 of
Note that if the total length of the optical path through guides 3008A, gate 3012A and guide 3016A matches the total length of the optical path through guides 3010A, gate 3014A and guide 3018A, then delay SA of gate 3020A may be equal to zero. Assuming, without any limitation, that SA=0. In such a case, for producing coincidence signal at output port 3022A, the coincidence signals of gates 3012A and 3014A should occur simultaneously. Simultaneous coincidence at gates 3012A and 3014A can occur only with information pulses 3044 (typ.) related to the currently demultiplexed time frame 3046. Information pulses 3044 related to adjacent time frames 3046 are delayed from reference pulses 3042A by a time space that is greater than the largest delay ΔtF in system 3000 and thus can not produce a coincidence pulse in gate 3012A at the same time gate 3014A produces a coincidence.
Accordingly, similar to the discrete coincidence gates in the demultiplexing systems of
It should be understood that coincidence gates 3012A–3012N, 3014A–3014N, 3020A–3020N, 30012M, 3014M and 3020M are all of the various types of coincidence gates 101 of
It should also be understood that all the discrete coincidence gates of the demultiplexing system related to the present invention such as the demultiplexing system of
Note that the data symbol signals for the combined coincidence gates of system 3000 include time-frame pulses 3042A (typ.) and 3042B (typ.) and information pulses 3044 (typ.) thus is constructed by more than two pulses. The number of pulses that may be used in the data symbol signals increases with the number of discrete coincidence gates used to construct the combined coincidence gate that uniquely decodes the data symbol signals.
A variety of embodiments of a gate 100 were discussed previously and will be summarized presently along with some others. As shown in
For example, referring to
Referring now to
The mechanical phase-shifting technique described with reference to
The client output signal 719 emerging from the beam splitter 722 is used in a system requiring the phase compensation provided by the phase shifter 720. Alternatively, the whole control apparatus of
Referring now to
An example of a client, e.g. 731A, is a gate 101 as described below with reference to
The process of synchronization and phase recovery may be reserved to a regular calibration process that is done at intervals sufficient to ensure the phase and synchronization remain proper. It is assumed that the processes upstream of the ports 601 and 603 of
Referring to
Referring to
Referring to
Referring to
It should be understood that gate 101 may represent any combination of coincidence gate 100 with or without its accompanied means described elsewhere according to the present invention. Such a combination may include coincidence gate 100 with more than one accompanied means. For example, gate 101 may include gate 100 with or without optical threshold device, contrast enhancers of various types used to enhance to increase the ratio between coincidence and non-coincidence signals or background, variable time delays, closed loop phase controls, closed loop clock recovery control, and other means described according to the present invention.
It should be noted that the inputs of gate 101, input 614 and input 616 are also schematically designated as lettered circles A and B. The outputs of gate 101, output 610 and output 612 are also schematically designated as lettered circles C and D. This notation shall be used throughout the various illustrations.
Referring to
It will be observed that the system may be configured such that the spacing of the coincidence symbols 626A, 626B, 626C and 626D is higher than the spacing of symbols in the signal 638A, not only by virtue of having been stripped of the pulse-spacing symbology, but, more importantly, as a result of reduction in the duty cycle (and therefore, the data rate) of each channel 642 (typ.) and therefore a reduction in the duty cycle of each receiver. As a result, if the spacing of symbols in the signals 638A is too low for any receiver to handle, for example, a receiver with an optical to electrical signal conversion process that includes transfer to storage, the incoming signal 638A will be divided among multiple parallel signals 624A–624D, providing a slower symbol rate in each than the combined signal 638A allowing the receiving processes to occur in parallel. Note that the signal 638A may necessarily lose intensity as a result of being divided among multiple channels and this may be compensated for by inclusion of an optical amplifier, in input B (not shown), without changing the operation of the device.
It should be clear that system 640 is a self demultiplexer that demultiplexes the information pulses in the symbols of input signal 638A. Each symbol of signal 638A includes an information (data) pulse and a control pulse. The self demultiplexing of the information in the symbols of signal 638A is performed by producing a coincidence pulse in a specific designated port (destinations D1–DN) that is responsive only to a specific predetermined destination encoded in the input symbols constructed by selecting the time space between the information (data) pulse and the control pulse.
Divider device 644 may represent any means for distributing the input signal from one input into multiple ports. Device 644 may be, for example, a star splitter/coupler, a cascade of one-to-two spliters/couplers, a cascade of one-to-many splitters, a loop having multiple ports, and a combination between all the means above.
It should be clear that while some of the splitters in
Referring now to
Referring now to
Note that instead of using a single mode locked laser to form a stream of pulses to multiple modulators, signals can be obtained from multiple mode locked lasers with a common cavity such that their signals are synchronized.
Note that six data channels have been chosen for illustration purposes only. This number, six, is chosen arbitrarily and has no practical limitation to the number of data channels (along with respective delays, modulators and symbolizers) that can be used.
In another alternative, a single mode locked laser 875 as shown in
In a steady state, the process of duplicating the pulses by loop 877 produces a train of identical narrow pulses. The process continues till another pulse 875E appears in signal 875A of mode locked laser's 875 output. Just before the appearance of such pulse, gate 878 may be turned activated to stop recirculation of a returned signal (pulse) in loop 877. After the termination of the pulse duplication and before the arrival of the next pulse 875E, gate 878 activated to block the pulse circulating in the loop 877 and to allow the beginning of a new duplication process. Again this continues till the next activation of gate 878 and the appearance of the next pulse of signal 875A. Gate 878 can be a shutter, an LCD window, a coherent summer receiving light from a source such that the pulse in the loop 877 is canceled, or any suitable device.
The interval between duplicated pulses is the time-space between duplicated pulses and is equal to the total delay of loop 877. To create a train of pulses equally spaced, the space between two following pulses 875E of signal 875A should be equal to an integral number of spaces between duplicated pulses and the delay of loop 877 has to satisfy this condition.
Gate 878 is activated to halt the last pulse to be repeated before a new pulse is generated by the mode locked laser 875. Gate 878 is deactivated to allow the passage of the new pulse generated by laser 875 which propagates in loop 877. Thus a narrower train of pulses 875B can be generated at output port 879E with only one delay device. This may allow the pulse train 804 (
Referring to
Here, as with
Referring now to
Referring now to
Note that a configuration like that of
Referring to
Optionally, to provide a non-zero background which when coherently summed as discussed with regard to
The CW signal 580 may be derived from the same source as modulated laser 843A which may be configured to provide one output that is not modulated, as illustrated in
In an alternative embodiment, the same role as signal 580 may be played by a laser 595 that is separate from laser 843A as indicated. In such a case the phase matching between laser 595 and the signal 843F may be controlled by a control mechanism for recovering the phase. For example, a detector 593 detects a portion of the power of the signal 843E taped into detector 593 and generates a feedback control input to a controller 591 that controls a phase shift by variable phase shifter 594 to maximize the signal power detected. Such a mechanism performs a function of Phase Locked Loop (PLL). As this is an alternative role for signal 580, it is marked in dashed lines and can be used instead of signal 580 and guide 580B.
Note that in the discussion of figurative illustration of signals, such as 843F and 843E, the same diagram may connote the field or the intensity, which is the square of the field. This should be clear from the context and no contradiction is implied. Thus, in indicating a shift in zero level from signal 584A to signal 585, signal 843F and 843E may be interpreted to represent the field level, but ignoring the zero level indication, they may be interpreted to represent intensity. Note that
Instead of providing a separate gate 3845 (typ.) on each channel 3847 (typ.), a single gate may be located immediately following the single output 843D of the modulated laser 843A to produce narrow pulses that are distributed to all the channels 3847 (typ.)
Referring now also to
As another example illustrated in
Referring to
Referring now to
Referring to
Referring now also to
Referring now to
Referring now to
Signals 912 (typ.) may represent encoded symbol for any number of layers and may be at any desired length. However for maintaining synchronization a specific fixed time frame may be defined capable of including the longest symbol 912 (typ.). Any time frame produces only one coincidence signal by the specific gate 101 (typ.) at the last demultiplexing/switching layer designed to respond to specific symbol 912 that the specific frame includes. Thus in order to maintain synchronization where the propagation of the signals is from left to right, each symbol 912 should start on the left edge of each time frame.
A guard interval between the time frame of symbols 912 (typ.) maintains a distance between adjacent time frames may be any width sufficient to prevent inter-symbol interference, for example, the maximum time delay used for a previous symbol. In case that the artifact pulses are cancelled, the guard zone requirement may only exist at the layer with the highest encoding delay. This is because the time delays that correspond to the other layers are always a fraction of the delay at this layer, the presence of the highest guard interval guarantees that no overlap will occur between successive symbols in the lower layers.
Note that, generally, in the foregoing illustrations, artifact pulses may be left out of signals, even though it may be present in certain embodiments, depending on the nature of the embodiment used for form the pulse-pair symbols.
Refer now to
Signal 930 is applied to the second layer of gates 952N-952R, each with a respective time delay Δtn–Δtr (illustrating specifically, for example, Δt2 that matches gate 952P). Gate 952P, which is within the range of gates 952N–952R (a range which also has an arbitrary number of gates within the confines of the encoding range), outputs signal 932 because it is configured for the matching time interval Δt2. Signal 932 may be thought of as containing the structure of one half of the signal 930 and results due to the coincidence effect described for coincidence gates above. The other gates in the layer 948 output no signal, because their time delays have non-matching values.
Signal 932 is applied to the third layer of gates 952V–952Z, each with a respective time delay Δt1–Δt2 (illustrating specifically, for example, Δt3 that matches gate 952�). Gate 952X, which is within the range of gates 952V–952Z (a range which also has an arbitrary number of gates within the confines of the encoding range), outputs signal 934, because it is configured for the matching time interval Δt3. Signal 934 may be thought of as containing the structure of one half of the signal 932 (or a single pulse) and results due to the coincidence effect described for coincidence gates above. The other gates in the layer 950 output no signal, because their time delays have non-matching values. Note that in
It also should be clear that the self decoding/demultiplexing/switching systems discussed above, such as the systems of
In addition it should be noted that the system of
The main coincidence signal is the coincidence pulse with the highest intensity that exists in the system for a specific symbol. While some other coincidence signals may be produced in the same gate where the main coincidence signal is produced or in other gates, still the main coincidence pulse is the pulse with the highest intensity produced in the system. A main coincidence pulse only outputs at a specific gate that matches the time delays between the pulses of a specific address of a specific symbol.
Note that each gate in the series of gates forming the combined coincidence gate of
Referring now to
It should be understood that when the device of
Referring now to
Each gate 1007A–1007C has a respective phase shifter 1010A–1010C that adjusts the phase so that coincidence pulses result from constructive interference, at couplers 1005A–1005C, provide the maximum ratio of pulse height to background (including non coincidence pulses).
When device 1000 is made from optical fibers, the phase shifters 1010A–1001C can be of the type that applies pressure, by use of a piezoelectric crystal. For device 1000 that is made using planar waveguides, the phase shifters 1010A–1010C can be of the type that thermally changes the refractive index of the waveguide, or semiconductor material fabricated by thin film techniques that change its refractive index due to injection of charge carriers into its guiding media. The change in the refractive index shifts the phase of the radiation propagating in the media of the shifters 1010A–1010C.
Phase matching can be obtained by use of a suitable calibration by closed-loop phase controller 1012. A calibration signal may be obtained from any of the signal paths, for example, by means of a detector 1016 that taps a small portion of signal energy from directional coupler 1005B. The detector 1016 and phase controller 1012 combination may provide an instantaneous or averaged signal and be configured to maximize intensity. Since most properties that affect the phases of the signals within a small embodiment of receiver 1000 are uniform, for example if formed on a chip, a change in properties that affects on signal path should affect all in the same way. Thus, the entire configuration of receiver 1000 may be calibrated such that only one detector is required to provide for control of all the phase shifters 1010A–1010C. Temperature changes, for example, in various optical components may drift, requiring the correction of the phase match. But this correction need only be done at long intervals relative to the rate of data throughput through such devices and therefore does not present a significant obstacle. Suitable control systems for performing calibration are well within the state of the art and can be embodied in many different forms.
Although in the embodiment of
Threshold inputs 1008A–1008C to respective comparators 1011A–1011C discriminate coincidence pulses from artifact and background by establishing a minimum signal level output from detectors 1006A–1006C. As a result, the comparators 1011A–1011C output pulses 1021A–1021C only when a coincidence pulse is received by them. The threshold inputs 1008A–1008C may be established by various methods. In one embodiment, a handshake from each sender occurs at regular intervals and a test message with a certain number of coincidence pulses and model artifact is sent many times while the threshold level is ramped up and down. Then some midpoint (or another point in the range between the intensities of the coincidence and artifact pulses) may be established in response to the test exchange and then the threshold level may be fixed thereafter in response.
It should be understood that the optical sensors and the electronic thresholds (comparators) components may be an integral part of the demultiplexing device, they may be placed in close vicinity to the demultiplexing device, they may be placed far away from the demultiplexing device, and even may be placed in an end unit. The same is true in the situation that optical thresholds are used to replace the combination of optical sensors and electronic threshold components. Such optical thresholds may be an integral part of the demultiplexing device, they may be placed in close vicinity to the demultiplexing device, they may be placed far away from the demultiplexing device, and even may be placed in an end unit.
Note that device 1000 may be fabricated from Multi Mode (MM) radiation guides, such as fibers or waveguides. In such a case the radiation in combiners 1005A–1005C is summed incoherently and there is no need for the phase control. Accordingly, when MM radiation guides are used in device 1000, detectors 1006A–1006C, controller 1012 and shifters 1010A–1010C may be removed resulting in a simpler device. Though MM device 1000 has the advantage of simplicity, it has a disadvantage of lower contrast between coincidence and artifact pulses.
Referring to
Fabrication of delay lines on a chip presents some problems because of the minimum radius of turns required to ensure tolerable band loss in the turns. The required radii and the requirement to avoid cross-intersection between the radiation guides may cause the amount of real estate required for large delays to be too great for practical manufacture and even if they can be manufactured, the waste of real estate would make such a configuration uneconomic. A configuration that is much more susceptible to convenient lithographic fabrication on a chip is shown in
Referring to
Referring to
In another variation shown in
It should be noted that in the configurations shown in
Referring now to
Referring now to
Referring now to
Referring now to
For demodulating, the symbols from common data path 1058D are distributed, by device 1058A, into an array of gates 1058B–1058C (typ. but with different delays ΔtZ–nΔtZ) and are demultiplexed by this array of gates in a manner similar to earlier embodiments.
Referring to
Referring to
Referring now to
Referring now to
First a stream of narrow pulses generated by means of any of the foregoing mechanisms is generated on each of a number of parallel channels 1228A–1228P. The spacing of the pulses (e.g., 1224B typ.) on each channel (e.g. 1228A typ.) may be equal to the size of the time slots multiplied by the number of channels and synchronized across all the channels 1228A–1228P such that every time slot has a single pulse in one of the channels according to a repeatable scheme. Modulators A–P 1122 (typ.) control whether pulses on respective channels 1228A–1228P are passed to a signal combiner 1226 to be emitted from port 1227. If all the pulses were passed by all the modulators A–P 1222 (typ.), the resulting train of pulses would be equally spaced pulses a single time slot apart. The modulators A–P 1222 (typ.) are all controlled by a controller 1230 to form spaced-pulse symbols according to a desired data stream (not indicated) on a single output channel 1227. The resulting signal, illustrated at 1226 may include a series that includes the pulse timing positions of pulses 1224A, 1224B, 1224C and others, illustrated by pulses 1225A, 1225B, 1225C and others, respectively, with the inter-symbol spacing as well as the selection of the symbol from the symbol space being determined by the controller and contributed to by all the channels in concert.
It is clear that using the same method, symbols including number of pulses greater than two, such as symbols 912, 940–944 and 1130–1134 of
In another embodiment, a similar system of
Note that although the above figures refer to the address symbols (e.g., 1071 of
The delay following each symbol that is required to prevent inter-symbol interference (called a guard band) may depend on the particular symbols and decoding gates used in the decoding system. For example, this may be the case when a pulse-spacing symbology is used with gates that allow artifact pulses as discussed below and shown in
Referring now to
Referring now to
Referring to
Using such a technique is very useful when multiple symbols are sent to the same destination. In such a case, a stream of pulses spaced by a specific time delay corresponding to a specific gate destination may be formed to direct information to this specific gate. In this case, each pulse serves double duty, as a pulse indicating the delay (time space) of a current symbol (data/control pulse) and as a reference pulse for the next following symbol (control/data pulse). This configuration allows saving in the number of pulses used to demultiplex information into the desired destinations.
The protocol of
Referring now to
A signal 1360 (
When pulses 1395 and 1385 of
Referring now to
As will be observed, by controlling the relative phases of pulses at two input ports, the port from which energy is emitted can be controlled. The above effect is used in several switching and gating systems that are now discussed. An illustration of a means by which the relative phase may be used for a symbology is illustrated in
It is clear that similar behavior may be achieved with other summing devices and especially with those illustrated by
Referring now to
Referring in particular to
It should be noted that the pulses in
Referring to
Pulse duplicators 1456A–1456F each duplicate an output pulse from a respective modulator 1453 (typ.) with a unique combination of pulse spacing plus phase difference as indicated by symbols 1470A–1470F. The latter are interleaved onto a common channel 1481 by a combiner 1468 which transmits it to a receiver 1482. The received signal from common channel 1481, which may be miles long or just a fraction of an inch, is distributed among multiple gates, exemplified by three 1471, 1472 and 1473. Each gate 1471, 1472 and 1473 has two outputs: 1471A and 1471B for gate 1471, 1472A and 1472B for gate 1472, and 1473A and 1473B for gate 1473. Each output 1471A and 1471B for gate 1471, 1472A and 1472B for gate 1472, and 1473A and 1473B for gate 1473 corresponds to a particular symbol 1470A–1470F such that only one will produce a coincidence pulse when a given symbol is sent through the common channel 1481. Each output 1471A and 1471B for gate 1471, 1472A and 1472B for gate 1472, and 1473A and 1473B for gate 1473 corresponds to a unique combination of pulse spacing 1542 indicated by time Δt (typ.), which selects one gate 1471, 1472 or 1473 and phase difference 1544 indicated by the phase φ (typ.) between the pulses, which selects the output 1471A or 1471B if gate 1471 is selected, 1472A or 1472B if gate 1472 is selected, or 1473A or 1473B if gate 1473 is selected. Note that pulses drawn upside down represent a phase shift of π radians.
As will be evident from the above description by using a combination of phase and time delay, the number of outputs that can be selected can be doubled over using time delay alone. Also, the dilution of signal energy is reduced by half because the pulse intensity is preserved across a gate that adds coherently and energy does not have to be diluted among ports of a given gate.
Referring now to
Referring now also to
Another summation 1547B occurs in gate 1533, which results in a coincidence signal 1543E and is output from output 1533A. Finally, yet another summation 1547C occurs in gate 1535, which results in a final coincidence signal 1543G and is output from output 1535A. It will be observed from the foregoing that the height of the coincidence pulse 1543H incurs substantially zero degradation through the gates 1530, 1533 and 1535 at ports 1530A, 1533A and 1535A, respectively, because phase is used to perform the gating through the successive layers.
It may be confirmed by inspection that the various pulses patterns 1540A–1540H shall propagate accordingly:
Pattern 1540A will produce a coincidence pulse at output 1535A as discussed above.
Pattern 1540B will choose output 1530B, but will thereafter propagate through 1532A and out from output 1539A.
Pattern 1540C will choose output 1530A of gate 1530 and output 1533B of gate 1533 and then output 1537A of gate 1537.
Pattern 1540D will choose output 1530B of gate 1530, output 1532B of gate 1532 and output 1541A of gate 1541.
Pattern 1540E will choose output 1530A of gate 1530, output 1533A of gate 1533 and output 1535B of gate 1535.
Pattern 1540F will choose output 1530B of gate 1530, output 1532A of gate 1532 and output 1539B of gate 1539.
Pattern 1540G will choose output 1530A of gate 1530, output 1533B of gate 1533 and output 1537B of gate 1537.
Pattern 1540H will choose output 1530B of gate 1530, output 1532B of gate 1532 and output 1541B of gate 1541.
As may be also be confirmed by inspection, the above binary tree format may be extended to any number of final outputs and the eight shown here was a number arbitrarily chosen for illustration.
While the above description contains many details, these should not be considered as limitations on the scope of the invention, but as examples of the presently preferred embodiments thereof. Many other ramifications and variations are possible within the teachings to the invention.
For example the all-optical switches, modulators, encoding and decoding systems, interleaving and multiplexing systems, and demultiplexing systems have been described for use in communication networks. However they can be used in other optical systems as well, such as systems used for optical backplanes, optical storage networks and optical computing. They also can be used as optical components, devices, and systems in Ethernet systems. Although the invention been described using the examples of Dense Time Division Multiplexing (DTDM) and self-triggered CDM it can be used for producing very narrow pulses to perform standard techniques, such as TDM, ATM and packets routing.
Although some systems have been described as modulators they also can be operated as switches. While some all-optical encoding and multiplexing systems have been described using sub-units operating as modulators, the situation can be reversed, i.e., the operation of these same sub-units can be change to serve as switches in decoding and demultiplexing systems. Though some switches and modulators have been described with one output they can include multiple outputs. While the modulators and the switches have been described as containing gratings or phase arrays, they can also include other interference devices that are capable of changing their pitch according to the illumination conditions. Although the gratings and phase arrays have been described as having one ore three interference orders, they are not limited to these numbers of interference orders. While some of the switches and the modulators are illustrated without optical amplifiers they can be integrated with optical amplifiers, such as a Europium Doped Optical Fiber Amplifiers (EDOFA), Solid-state Optical Amplifiers (SOA) or Linear Optical Amplifiers (LOA).
While some coincidence gates are illustrated when receiving the signal at their inputs from a single source they may receive the signals from different sources.
While some of the embodiments illustrated in media of open space, radiation guides, fiber optics, waveguides, planar waveguides on a chip, each of them may be produced in any of these media.
Thus the scope of the invention should be determined by the appended claims and their legal equivalents, and not by the examples given.
It will be evident to those skilled in the art that the invention is not limited to the details of the foregoing illustrative embodiments, and that the present invention may be embodied in other specific forms without departing from the spirit or essential attributes thereof.
The present embodiments are therefore to be considered in all respects as illustrative and not restrictive, the scope of the invention being indicated by the appended claims rather than by the foregoing description, and all changes which come within the meaning and range of equivalency of the claims are therefore intended to be embraced therein.
|Cited Patent
|Filing date
|Publication date
|Feb 28, 1997
|May 4, 1999
|Koninklijke Ptt Nederland N.V.
|Optical packet-switched transmission network
|Feb 9, 1999
|May 2, 2000
|Tyco Submarine Systems, Ltd.
|Synchronous polarization and phase modulation for improved performance of optical transmission systems
|Jul 27, 1999
|Aug 13, 2002
|Sycamore Networks, Inc.
|Method and apparatus for improving transmission performance over wavelength division multiplexed optical communication links using forward error correction coding
|Feb 19, 1997
|Dec 10, 2002
|Canon Kabushiki Kaisha
|Transmission control method in a network system for interactively transmitting a signal between node devices and network system using the same
|Jan 4, 2001
|Mar 23, 2004
|Nippon Telegraph And Telephone Corporation
|CDMA encoder-decoder, CDMA communication system, WDM-CDMA communication system
|Dec 21, 2001
|Nov 14, 2002
|Quellan, Inc.
|Increasing data throughput in optical fiber transmission systems
|Citing Patent
|Filing date
|Publication date
|Apr 22, 2004
|Nov 27, 2007
|Finisar Corporation
|Optical transceiver and host adapter with memory mapped monitoring circuitry
|Jun 21, 2002
|Mar 9, 2010
|Alcatel-Lucent Usa Inc.
|Method and system for multiplexed optical information transport
|Jul 1, 2008
|Apr 17, 2012
|Finisar Corporation
|Diagnostics for serial communication busses
|Apr 17, 2012
|Mar 26, 2013
|Finisar Corporation
|Diagnostics for a serial communications device
|Jun 1, 2010
|Aug 27, 2013
|University Of Central Florida Research Foundation, Inc.
|Optoelectronic logic gate
|Aug 28, 2012
|Oct 20, 2015
|Genia Photononics Inc.
|System and method for synchronizing light pulses at a selected location
|Apr 22, 2004
|Feb 10, 2005
|Light Greta L.
|Optical transceiver and host adapter with memory mapped monitoring circuitry
|Jun 1, 2010
|Dec 2, 2010
|University Of Central Florida Research Foundation, Inc.
|Optoelectronic Logic Gate
|May 13, 2011
|Mar 7, 2013
|France Telecom
|Optical line termination device allowing the implementation of an ofdm modulation technique
|U.S. Classification
|398/46, 398/75, 398/152, 398/214, 398/183, 398/212, 398/166, 398/57
|International Classification
|Cooperative Classification
|European Classification
|Aug 14, 2003
Owner name: PRIMA LUCI, INC., NEW YORK
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:SHAHAR, ARIE;HALBERTHAL, ELDAN;REEL/FRAME:014396/0863
Effective date: 20030814
|Jun 28, 2006
Owner name: MAIN STREET VENTURES LLC, NEW YORK
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:PRIMA LUCI INC.;REEL/FRAME:018083/0055
Effective date: 20060127
|Feb 23, 2010
|Fee payment
Year of fee payment: 4
|Apr 13, 2014
|Fee payment
Year of fee payment: 8


text:
Body Wraps and Scrubs DiplomaShow All Courses >>
This one day course is great starting point for therapist wishing to introduce spa therapy to their regular clients. Students will do all the theory behind the treatment and will be shown the correct technique and application of the exfoliation and body wrap.
The course has been designed by Sumita Singh, our founder. She is an industry expert on body wraps and has lectured on this at beauty shows also publishing many articles on this in various trade magazines.
The qualification is designed to provide occupational capability to provide a sound platform onto further learning or training
- Course
- Accreditation &
Entry Requirements
- Cost includes
- Exams
- Progression
This one day course covers:
- Introduction to Spa Therapies
- General effects of Spa Therapies
- Anatomy and Physiology (effects of heat on the body)
- A-Z of Spa Treatments
- Contraindications
- Client consultation and preparation of treatment
- Health & Safety within the Spa
- How to apply a scrub
- How to provide a body wrap treatment
- Contractions
- Homecare and aftercare advice
At Affable Therapy Training, we understand the need to conduct classes in small groups. We also understand that learners learn differently therefore course material is delivered in various ways, e.g. PowerPoint presentation, group work, detailed course manual with diagrams, other activities to keep learners engaged throughout the day. Our teachers are qualified and have years of experience in their chosen field. They bring their knowledge and passion to the class to inspire and encourage the learners. Lessons are carefully planned around learner needs making our courses very effective.
This course is accredited by the Guild of Beauty Therapy. Candidates have to have level 2 Beauty and accredited Anatomy and Physiology qualification to start this course.
- One day tutor led practice
- Detailed Course Manual with diagrams
- Materials supplied on the day.
- Course Certificate
- Friendly and safe learning environment
- Professional training facilities
There is no exam for this course. The assessment is done on tutor observation. Upon successful completion you will receive your certificate at the end of your course.
Ones learner have achieved the Certificate in Body Treatments they may progress on to our ITEC level 2 or Level 3 qualifications.
Grace Smith
It was amazing to go to Beauty UK and listen to Sumita lecturing on anti-cellulite techniques and body wraps. I was so impressed that on my return I booked my one day course. The teaching facilities were good and I learnt a lot more on the course. Sumita is an industry expert in this field and helped me tailor the techniques to my working environment.
28/08/2014 02:33:59


text:
2016 TripAdvisor Certificate of Excellence winner La Quinta Inn and Suites Fort Myers Airport, off I-75, is close to Gulf Coast Hospital, Lee Memorial Hospital, Lee Civic Center, Edison Community College, and Southwest Florida College. Rooms feature refrigerator and microwave. Enjoy free Ultra Fast wireless internet, daily free Bright Side Breakfast, free parking, barbecue grills, indoor pool, and business and fitness centers. Meeting room seats 60. All rooms are nonsmoking. Pets are free.
Pet Policy
Pets stay FREE at La Quinta! Domestic pets, like cats and dogs, are welcome to stay at La Quinta. While rooms are spacious, no more than two (2) domestic pets are allowed per room. Be sure to keep your pets on a leash or in a carrier if they're outside your room. Pets may remain alone in a guestroom so long as the pet is well-behaved. With the exception of authorized service animals, pets are not allowed in the breakfast area, the fitness center and the laundry room or at the pool. If your cat is staying with you, you'll need to provide a litter box.
ReservationsBook Online or call 239-466-0012
Address & Contact:
9521 Market Place Road
Fort Myers, FL 33912
United States
9521 Market Place Road
Fort Myers, FL 33912
United States