text:
|Publication number
|Publication type
|Application number
|Publication date
|Aug 21, 2003
|Filing date
|Dec 30, 2002
|Priority date
|Feb 21, 2002
|Also published as
|Publication number
|Simon Atkinson, Palle Birk, Stacy Ho, Zoran Zvonar, Aidan Cahalane
|Original Assignee
|Simon Atkinson, Palle Birk, Stacy Ho, Zoran Zvonar, Aidan Cahalane
|Export Citation
|BiBTeX, EndNote, RefMan
|Patent Citations (5), Referenced by (19), Classifications (36), Legal Events (4)
|External Links: USPTO, USPTO Assignment, Espacenet
[0001] The present invention relates to device architecture of mobile telephony units.
[0002] There are an emerging number of standards for cellular communication. For example, the European GSM system works in transmission bands known as GSM 850, GSM 900, GSM 1800 and GSM 1900, where the numeric part of the name is indicative of the frequency of the band expressed in MHz. Furthermore, the UMTS system operates on a transmission band between 1.92 and 1.98 GHz. It would clearly be desirable if a telecommunications device could easily switch between these various telecommunications standards depending on which service it wished to use, or indeed which service was available.
[0003] According to a first aspect of the present invention, there is provided a transmitter for GSM and UMTS comprising: an in-phase/quadrature up-converter for mixing in-phase and quadrature inputs with an intermediate frequency; a GSM path including a phase locked loop; and a UMTS path;
[0004] wherein a frequency generator module is provided to generate a first signal at a frequency F1, and the first signal is supplied as an input to an image reject mixer in the GSM path, to a mixer in the UMTS path, and as an input to divider which divides the first signal by three to create an intermediate frequency which is supplied to the in-phase/quadrature up converter; and wherein the image reject mixer in the GSM path is controllable to select either an upper or lower side band such that the GSM path operates at either (1+⅓)F1 or (1−⅓)F1; and wherein the mixer in the UMTS path selects the upper side band so as to have a output at (1+⅓)F1.
[0005] It is thus possible to provide a transmitter arrangement operable in both the GSM bands, and the UMTS band in which many of the RF components are shared. Thus, for example, if the first signal from the frequency generator is in a band centered about 1.35 GHz, but extending as low as 1.28 GHz and as high as 1.485 GHz then it is possible to tune the transmitter to selectively operate in the GSM 850 and GSM 900 bands, and in the GSM 1800 and 1900 bands and in the UMTS band between 1.92 and 1.98 GHz.
[0006] Advantageously the first radio frequency signal is in fact generated by a ultra high frequency voltage controlled oscillator working in the range of 2.565 to 2.97 GHz. This frequency can then be divided by 2 by a divider in order to ensure that the first RF frequency has an equal mark space ratio. It will be appreciated by the person skilled in the art that transistor switching and logic technologies are now fast enough to operate at these frequencies. Furthermore, the divider can be arranged to produce in-phase and quadrature versions of the first radio frequency signal.
[0007] Advantageously the divider for generating the intermediate frequency (i.e. a local oscillator signal) is a regenerative divider which comprises two channels, one working on the in-phase signal and one working on the quadrature signal. Each channel has a mixer which receives the first radio frequency signal and a divide by 4 circuit which receives an output of the mixer and which itself provides an input to a respective second input of the mixer. The output of the divide by 4 divider is also provided to the respective in-phase and quadrature mixers. The feedback loop formed by the mixer and the divider by 4 divider in fact forms a divide by 3 mixer, as is known to the person skilled in the art.
[0008] Preferably the GSM transmission path comprises a phase sensitive detector having a first input for receiving an output of the in-phase/quadrature up-converter, and a second input for receiving an output of the image reject mixer in the phase locked loop. An output of the phase sensitive detector is provided to an input of a voltage controlled oscillator which in turn generates a radio frequency output signal. The output of the voltage controlled oscillator is provided to a further input of the image reject mixer. Because the image reject mixer receives both the in-phase and quadrature signals of the first signal, it can be electronically selected to output either the upper side band or the lower side band. Thus the phase locked loop can be selectively locked to a frequency of F1 minus the intermediate frequency or F1 plus the intermediate frequency.
[0009] The output of the voltage controlled oscillator in the GSM path is also provided to a high power amplifier which can be driven in Class C mode in order to obtain high efficiency. Driving the amplifier in Class C mode generates harmonics at multiples of the frequency of the voltage controlled oscillator. However it is apparent that these multiples are spaced apart by at least 850 MHz and therefore can be easily removed by relatively simple filtering.
[0010] The UMTS path may comprise one or more electronically controlled variable gain amplifiers serving to amplify the modulated intermediate frequency signal. The amplifiers typically only have to operate across a relatively narrow band of frequencies centered about the intermediate frequency, e.g. 450 MHz. The amplifiers can therefore be constructed to be particularly linear. The output from the amplifiers is then mixed with the first signal by a single side band mixer in order to up-convert it to the UMTS output frequency in the range of 1.92 to 1.98 GHz. The output from the mixer may then be passed through a further variable gain amplifier giving around 25 to 30 dB of gain. The output of the amplifier may be passed through a surface acoustic wave filter before being supplied to a further off-chip power amplifier. A feedback path is also provided for sampling the output of the power amplifier, detecting the output level thereof, digitizing it through an analog to digital converter and providing a measurement of the power output to a UMTS power control logic circuit.
[0011] It is thus possible, in a preferred embodiment of the invention, to provide a multimode transmitter operable in both UMTS and GSM transmission modes, the transmitter comprising:
[0012] a. a signal input for receiving a signal (such as an I/Q baseband signal) to be upconverted by the transmitter;
[0013] b. an oscillator for generating a first radio frequency signal having a frequency F1, where F1 is 1.5 or 0.75 times the desired carrier frequency FC;
[0014] c. a first divider for receiving the first radio frequency signal F1 and dividing it by three so as to form an intermediate frequency local oscillator signal, IF, having a frequency substantially at 0.25 or 0.5 times the desired carrier frequency;
[0015] d. at least one mixer for mixing the signal from the signal input with the intermediate frequency local oscillator signal to create a modulated intermediate frequency signal;
[0016] e. a GSM path responsive to the modulated intermediate frequency signal; and
[0017] f. a UMTS path responsive to the modulated intermediate frequency signal;
[0018] wherein the GSM path comprises a voltage controlled oscillator within a phase locked loop, the phase locked loop including an image reject mixer receiving at a first input thereof the output of the voltage controlled oscillator, and at second inputs thereof in-phase and quadrature representations of the first radio frequency signal, such that it selectively outputs either the upper or lower side band as the signal to the phase sensitive detector within the phase locked loop; and
[0019] wherein the UMTS path comprises at least one variable gain amplifier and a mixer for mixing the first radio frequency signal with the modulated intermediate frequency signal and outputting one of the side bands to a further amplifier stage.
[0020] The oscillator may be followed by a divide by two stage such that in-phase and quadrature versions of the divided oscillator signal can be easily obtained. In such an implementation the oscillator frequency needs to be doubled to 1.5 or 3 times the desired carrier frequency.
[0021] According to a second aspect of the present invention, there is provided a direct conversion multi-mode receiver comprising electronically reconfigurable filters.
[0022] It is thus possible, by providing reconfigurable filters, to manipulate the output from the direct conversion multi-mode receiver such that it is suitable for additional processing operations to be performed on the signal in order to extract the data therein.
[0023] Advantageously the direct conversion multi-mode receiver also comprises offset generators which can be used to apply a controllable offset to a summer which is responsive to the output of the receiver.
[0024] In the direct conversion topology, it is highly desirable in order to be able to provide an offset to the output from the receiver. A reason for this is that the down conversion is performed by mixing the received radio signal, which is nominally centered about a frequency Fr, with a locally produced radio signal, also having a frequency of Fr. It therefore follows that the carrier of the received signal is down converted to a DC signal (or very near DC in the case of oscillator frequency mismatch). Any spurious DC offset (or low frequency signal) therefore needs to be subtracted from the output of the converter in order to reduce the dynamic range required of the subsequent processing circuitry, which in reality will comprise analog to digital converters such that further processing can then be performed in the digital domain. The act of removing the DC offset means that the dynamic range and resolution of the converters required can be reduced, therefore reducing the cost of the subsequent processing circuitry.
[0025] In a preferred embodiment, a direct conversion multi-mode receiver is provided which comprises at least one electronically reconfigurable filter arranged to filter a base band signal received from the receiver, and an offset generator, each of the reconfigurable filter and the offset generator is under the control of a control circuit such that the offset and filter response can be automatically controlled as a function of reception mode and signal conditions.
[0026] The filter may be implemented in hardware or software. Hardware implementations will tend to be preferred as they do not place so great a load upon post ADC processing resources.
[0027] According to a third aspect of the present invention, there is provided a hybrid filter exhibiting substantially uniform group delay in a pass band thereof, wherein the filter comprises a combination of a Chebychev and an inverse Chebychev response.
[0028] When designing an analog filter for communications applications, there are generally difficult trade-offs to be made between requirements for selectivity, group delay and complexity. Ideally, we want the physical delay for a signal passing through the filter to be uniform irrespective of its frequency content. Thus, in terms of a phase versus frequency graph, the phase delay needs to increase linearly with frequency.
[0029] In the context of telecommunications, and in particular UMTS communications, it is important that differential group delay be avoided as this can give rise to inter-symbol interference.
[0030] However, it is also generally necessary to obtain good selectivity, that is a rapid transition between the pass band and stop band.
[0031] It is well known that high Q filters that display good selectivity performance such as Chebychev and Elliptic filters often suffer in terms of differential group delay performance. On the other hand, filters that exhibit good differential group delay performance such as Butterworth and Bessel filters generally have inferior roll-off characteristics. The inventor has realized that combination of different filter characteristics can be arranged to give a desired response. The new filter design avoids the draw backs of conventional filter technologies and provides excellent selectivity, attenuation and differential group delay characteristics. The inventor has noted that the inverse Chebychev pass band characteristics are substantially identical to those of the Butterworth, but the filter contains stop-band zeros which give superior initial roll-off performance. On the other hand, the Chebychev filter has good initial roll-off characteristics and very high levels of ultimate attenuation.
[0032] Turning to the group delay characteristic, it is known to the person skilled in the art that at frequencies well below the cut-off frequencies, both the Chebychev and inverse Chebychev filters exhibit substantially uniform group delay. However, in the region of the cut-off frequency the first derivative of the group delay for the two different filters has opposite signs. The inventor has realized that by combining the two characteristics it is possible to achieve substantial cancellation of the group delay characteristics in the region near the cut-off frequency. This cancellation can be arranged to be sufficient to ensure that by the time the group delay cancellation begins to fail, thereby resulting in undesirable group delay characteristics, the magnitude of the signals have been sufficiently attenuated at these frequencies such that they become relatively unimportant.
[0033] The hybrid filter represents a good choice for a reconfigurable switched band multimode filter whose modes of operation may place differing demands on the filter performance. Thus, in the context of a multi-mode receiver, one mode of operation may place stringent requirements on the filter in terms of differential group delay, but not such difficult requirements in terms of selectivity. The other mode of operation might have more stringent requirements in terms of selectivity, but less difficult requirements in terms of differential group delay. The hybrid Chebychev/inverse Chebychev filter proposed here is an effective solution for both requirements. In addition to band switching the filter, it is also possible to adjust the relative cut-offs of the two constituent filters further optimizing performance in different modes of operation.
[0034] According to a fourth aspect of the present invention there is provided a dual mode single chip transceiver comprising a transmitter and a receiver, wherein frequency synthesizers are shared by the transmitter and the receiver, wherein the transmitter comprises an up-converter for receiving an input and up-converting it by mixing the input with a first synthesized frequency, and wherein in a GSM mode an offset phase locked loop is used to translate phase modulation at the up-converter output onto an RF carrier, and in a UMTS mode the up-converted signal is linearly amplified; and wherein the receiver comprises at least one direct down-converting channel for down converting the received signal.
[0035] It is thus possible to significantly reduce the implementation cost of a dual mode GSM/UMTS transceiver architecture by sharing many of the transmit and receive components within an integrated circuit.
[0036] Preferably the UMTS transmitter includes a further frequency up-conversion stage. Thus a first up-converter may produce an output at an intermediate frequency. The intermediate frequency may then be linearly amplified before being frequency up-converted to a final output frequency. This final output frequency may then be passed to a power amplifier which is not integrated with the integrated circuit. The provision of one or more power amplifiers "off-chip" reduces the signal leakage between the transmitter path and the receiver paths. This is particularly important as UMTS operates in full duplex mode and consequently signal leak through could have a degrading effect on receiver performance.
[0037] Preferably the UMTS duplex filter is also provided off-chip.
[0038] According to a fifth aspect of the present invention there is provided an automatic gain controller for a multi-mode homodyne receiver, the controller comprising an open loop controller responsive to a first signal for setting an initial gain, and a closed loop controller responsive to a measurement of signal power or amplitude for maintaining the signal power or amplitude at an output of the variable gain amplifier within a predetermined range.
[0039] It is thus possible to use an open loop controller to provide a rapid initial set up of the amplifier in order to bring it to roughly into a desired operational state, and then to "fine tune" the gain of the amplifier using a feedback loop. This enhances the set up time of the amplifier when changing mode.
[0040] UMTS radio systems require continuous full duplex operation. As part of this, automatic gain control (AGC) is required to maintain acceptable performance under varying signal level and channel conditions. The use of a homodyne architecture places certain constraints on the way in which the automatic gain controller can operate.
[0041] Homodyne receivers are susceptible to generating unwanted DC offsets in the in-phase/quadrature analog base band paths thereof. In order to maintain acceptable performance it is necessary to remove these DC offsets as they are indistinguishable from an on-channel signal. Under weak signal conditions, it is quite normal for the DC offset to be substantially larger in magnitude than the wanted signal. Thus, if the DC offsets were not removed, acceptable reception of the wanted signal is likely to prove impossible. A common approach to removing such offsets in wide band receivers is to use simple high pass filters or AC coupling (DC blocking) circuit arrangements.
[0042] Automatic gain control is achieved in homodyne receivers by adjusting the gain of analog base band amplifiers. However, adjusting the gain also adjusts the DC offset levels and thus creates a transient settling time problem with high pass filters which were introduced in order to block the DC component. As a consequence, a low band-width automatic gain control loop is desirable in order to minimize transient effects as these would occur as a result of shifts in the DC offset. However a low band-width automatic gain control is incompatible with the requirement for initial rapid acquisition of the signal.
[0043] The inventor has realized that it is possible to overcome this with a combination of a "feed-forward" or open loop automatic gain controller and a feedback automatic gain controller.
[0044] The feed-forward/open loop controller can either set up its initial values based on an initial measurement of the signal power made by a suitable measuring device, such as a full wave or half wave rectifier located at a suitable place in the receiver, for example at the output of channel select filters, or alternatively the open loop controller may make an initial gain control setting based on the desired mode of operation of the receiver. The open loop controller only operates once, at each mode change, to set up the initial parameters of the variable gain amplifiers and other components which may require gain set up. From then on, control is passed to the closed loop which makes fine adjustments to the various gain levels.
[0045] According to a further aspect of the present invention, there is provided a homodyne receiver comprising a high pass filter having a variable time constant and a variable gain amplifier, the filter and amplifier being upstream of an analog to digital converter, wherein when a step change of the gain of the variable gain amplifier is implemented the time constant of the high pass filter is reduced for a predetermined time period.
[0046] According to a further aspect of the present invention, there is provided a homodyne receiver comprising at least one signal conditioner upstream of an analog to digital converter and a high pass filter having a variable time constant, wherein when the at least one signal conditioner is operated to cause a variation to be made to the signal supplied to the analog to digital converter, the time constant of the filter is set to a reduced value.
[0047] The highpass filter may be implemented downstream of the analog to digital converter and may therefore be implemented in the digital domain.
[0048] In a homodyne direct conversion receiver, it is necessary to use a high pass filter to remove DC offsets from the analog base band signal paths. For a 3.84 MHz UMTS signal, the cut-off frequency for this high pass filter should be in the order of 10 kHz or so in order to remove the minimum level of the wanted signal energy. However, such a low cut-off frequency implies a long settling time for DC transients. The inventor has realized that the settling time for DC transients can be much improved if the cut-off frequency of the filter is temporarily increased. This significantly enhances the receiver settling time.
[0049] The present invention will further be described, by way of example, with reference to the accompanying drawings, in which:
[0050]FIG. 1 is a circuit diagram schematically illustrating a combined GSM and UMTS transmitter, with shared RF components integrated into a single circuit;
[0051]FIG. 2 is a schematic diagram of the direct conversion multi-mode receiver;
[0052]FIG. 3 is a graph comparing the group delays of low pass Chebychev and inverse Chebychev filters versus frequency;
[0053]FIG. 4 is a graph of the magnitude response of low pass Chebychev and inverse Chebychev filters versus frequency;
[0054]FIG. 5 shows the combined magnitude response of the filters of FIG. 4;
[0055]FIG. 6 schematically illustrates a combined GSM/UMTS transceiver; and
[0056]FIG. 7 schematically illustrates an automatic gain control.
[0057]FIG. 1 schematically illustrates transmitter circuitry according to an embodiment of the first aspect of the present invention. The transmitter can be selectively operated as either a dual band GSM transmitter, or alternatively as a 3G UMTS transmitter. The transmitter comprises a single chip 1 on which is located a single radio frequency synthesizer 3. In accordance with an input signal fin received by the synthesizer 3, the synthesizer controls a local oscillator 5 such that the oscillator 5 produces a substantially fixed frequency signal that is at either 1� or 3 times the desired carrier frequency, depending on the actual desired operating frequency for the GSM or UMTS transmission path. It should be emphasized that the actual frequency of the signal generated by the general oscillator 5 does not substantially differ depending upon the band of transmission, only its ratio to the desired carrier frequency. The frequency of the signal generated by the local oscillator 5 may, for example, be approximately 2.7 GHz and more specifically in the range of 2.565 to 2.970 GHz. This corresponds to a modest adjustment of �10% (in fact around 7% in this example) of the frequency generated by the local oscillator.
[0058] The signal from the local oscillator 5 is then fed to a frequency divider 7 that divides the frequency of the signal by 2. The frequency divider 7 also allows the signal to be split into in-phase (I) and quadrature (Q) components. The I and Q components are fed into a further frequency divider 9 in the form of a regenerative divider that is arranged to divide the input frequency by 3. The divide by 3 frequency divider 9 comprises a frequency mixer 11 that receives the I and Q components of the input frequency signal and mixes them with corresponding components of the same signal that have been further frequency divided by 4 by a further frequency divider 13. The arrangement of the mixer 11 and divide by 4 divider 13 produces a divided by 3 frequency signal of the original input signal at the output of the divide by 4 divider 13. The I and Q components output from the divide by 3 divider 9 are therefore at � or � of the carrier frequency. Taking our example of the input frequency fin of 2.7 GHz, the I and Q components at the output of the divide 3 divider 9 are at 450 MHz.
[0059] The individual I and Q components are supplied to respective individual mixers 15 and 17 that each also receive the respective I and Q components of the analogue source signal. The mixers 15 and 17 act to combine the respective source signal components together with the I and Q components at 450 MHz to generate a 450 MHz modulated intermediate frequency signal which it then passed through a bandpass filter 19.
[0060] The intermediate frequency at the output of the bandpass filter 19 is then propagated along two individual signal paths, each path being used to generate respectively the GSM signal or the 3G UMTS signal.
[0061] For GSM, the 450 MHz intermediate frequency signal is fed to a first input of a phase comparator 21. The second input of the phase comparator 21 also receives a 450 MHz signal that is received from a bandpass filter 23. The input to the bandpass filter 23 is derived from an image reject mixer 25. The image reject mixer 25 receives as first inputs the I and Q components of the 1.35 GHz signal that is obtained from the combination of synthesizer 3, local oscillator 5 and divide by 2 divider 7. The other input to the image reject mixer 25 is the carrier frequency signal that is generated by a voltage controlled oscillator 27 that is in turn controlled by the output from the phase comparator 21. The phase comparator 21, voltage controlled oscillator 27 and image reject mixer constitute a phase locked loop that is used to translate the modulated intermediate frequency to the radio frequency carrier signal. The phase locked loop acts as a tracking bandpass filter and thus removes the need for an RF bandpass filter such as a SAW or ceramic filter that would otherwise be required to minimize out of band emissions.
[0062] The carrier frequency is substantially either 900 MHz or 1.8 GHz, depending upon the GSM band on which it is desired to transmit. The image reject mixer can selectively either subtract the 900 MHz signal from the 1.35 GHz I and Q component signals to arrive at the 450 MHz signal input to the bandpass filters 23, or to subtract the 1.35 GHz from the 1.8 GHz carrier signal, thus also arriving at a 450 MHz output. Thus the two signals input to the phase comparator 21 are always at 450 MHz, i.e. the intermediate frequency. It is thus possible to cover the GSM 850/900 range and the GSM 1800/1900 range.
[0063] The modulated GSM signal is applied to a high power amplifier 29 that receives a power control signal on an input line 31. The output of the amplifier 29 is fed to an antenna 33 via a switch 35.
[0064] For 3G UMTS transmission, the intermediate frequency signal output from the 5 bandpass filter 19 is fed through a pair of serially connected variable gain amplifiers 37, 39 prior to being mixed with the 1.35 GHz signal derived from the local oscillator 5 and divide by 2 divider 7. The two signals are mixed at a single side band mixer 41 to produce a 1.8 GHz signal that is itself further amplified using a further single variable gain amplifier 43. Amplifiers 37, 39 and 43 are controlled using a power control circuit 45 that receives a sampled and digitized input signal representative of the power of the transmitted output signal obtained via a tap at the output of amplifier 49. The 1.8 GHz signal from the power amplifier 43 is passed through a UMTS RF SAW filter 47 and a further UMTS power amplifier 49 before being transmitted via the antenna 33. The signal is also passed through a duplexer and isolator unit 51 connected between the antenna and the UMTS power amplifier 49 which selectively allows a received signal at the antenna to be directed towards a receiver circuit.
[0065] The great advantage of the circuit described above is that a single RF synthesizer, running at 2.7 GHz in the above example, is all that is required for the generation and transmission of both a dual mode (850/900 and 1800/1900) GSM signal and a 3G UMTS signal. The use of the dividers and mixers ensures that the desired carrier and output frequencies are always at fixed multiples of the synthesizer frequency. Thus is possible to provide a combined dual mode GSM and 3G UMTS transmitter in a single circuit that has a relatively large number of common circuit components for both transmission paths.
[0066]FIG. 2 schematically illustrates a direct conversion (also known as homodyne) multi mode receiver. The receiver comprises two channels, generally indicated 100 and 102 for convenience. Schematically, the channels are identical so only the first channel will be described in detail for convenience. However, in terms of operating performance, the channels may operate at different frequencies, for example around 800 to 1000 MHz for GSM 850 and GSM 900 and around 1.7 to 2.2 GHz for GSM 1800, GSM 1900 and UMTS. In these circumstances the individual components of the channels may be tailored in order to operate at their respective bands. Each channel comprises a band pass filter 110 and 110 a which serves to reject signals outside the pass band of the receiver. Thus, the filter 110 for the first channel 100 may be centered 900 MHz, whereas the filter 110 a for the second channel 102 may be centered around 1.8 GHz or so. These filters are necessary to stop powerful out of band transmissions from driving the receiver into saturation. The output of the band pass filter 110 is provided to an input of an amplifier 112 whose output is provided to the first inputs of mixers 114 and 116, respectfully. Second inputs of the mixers 114 and 116 receive in-phase and quadrature versions of a locally generated carrier signal. The in-phase and quadrature versions of the signal are generated by a phase shifter 118 which itself receives the locally generated signal from the combination of a multi mode fractional synthesizer 120, a voltage controlled oscillator 122 and a multi mode fractional frequency multiplier 124. The components 120, 122 and 124 are shared by each of the channels 100 and 102. The mixers 114 and 116 mix the locally generated reference signal together with the received radio signal in order to form the difference frequency therebetween. Since both the radio frequency and the locally generated frequency are nominally at the same frequency, the information in the radio frequency is directly down converted to base band. The base band signal is provided at the output of each of the mixers 114 and 116. The outputs of the in-phase mixers 114 and 114 a are provided to a first input of an in-phase summer 130 which is shared between both channels. Similarly, the outputs of the quadrature mixers 116 and 116 a are provided to the first input of a quadrature summer 132 which is also shared between both channels. Each of the summers 130 and 132 is also connected to receive an offset signal generated by a respective digital to analog converter 134 and 136. The ability to provide an offset is important since local oscillator coupling to the RF inputs could generate a DC offset, the size of which depends on both the magnitude and phase of the spuriously coupled signal with respect to the locally generated reference. The output of the summer 130 is provided to the input of an electronically controlled low pass filter 140 which in turn is followed by an electronically controlled variable gain amplifier 142. Similarly the output of the summer 132 is provided to an electronically controlled low pass filter 150 and a variable gain amplifier 152. The outputs of the amplifiers 142 and 152 are provided to respective analog to digital converters 160 and 162 whose digital outputs, after filtering in respective finite impulse response filters are provided to a signal processing and control unit 170. For each of the in-phase the quadrature channels, the control unit estimates the offset that is required for each of the channels and provides an offset signal to the digital to analog converters 134 and 136. The control unit 170 also sets up the filter characteristics of the switched filters 140 and 150 in the way appropriate to the operating mode of the receiver.
[0067] It is thus possible to provide a multi mode direct conversion receiver architecture as shown in FIG. 2. The architecture has the advantage that much of the receiver hardware is reused for different modes of operation. The reuse of common hardware can provide a significant cost and power saving when compared with duplicating functionality as has hitherto been the case.
[0068] The analog base band sections are designed so that they can be reconfigured to meet the requirements of the various transmission systems. This means that the architecture must allow for the:
[0069] i. reconfiguring of the gain line up,
[0070] ii. reconfiguring of the channel filters
[0071] iii. reconfiguring of the analog to digital converters speed and resolution, and
[0072] iv. reconfiguring of the DC offset compensation
[0073] As noted hereinbefore separate radio frequency low noise amplifiers and in-phase/quadrature down converters are utilized as these need to be optimized for the frequency and mode of operation. Although in principle it is practical to have a reconfigurable RF front end for different modes of operation, it is believed to be more cost effective at the present time to have dedicated RF front ends.
[0074] As noted hereinbefore, it is highly desirable that the analog processing circuitry within a mobile telephone has filters included therein which can give both rapid attenuation between the pass band and the stop band, and which also exhibit good group delay, and specifically do not exhibit differential group delay so as to avoid inter-symbol interference. FIG. 3 compares the group delays of an inverse Chebychev filter, represented by line 200, and the group delay of a Chebychev filter, represented by line 202, plotted as a function of frequency. Frequency units have been included on the ordinate of FIGS. 3, 4 and 5 such that the various graphs can be easily compared. It will be seen that, in the example given in FIG. 3, the inverse Chebychev group delay starts to increase for frequencies in excess of 2�105 radians per second. However, the Chebychev group delay starts to decrease for angular frequencies in excess of 2�105 radians per second and this decrease continues until the frequency 106 radians per second, then the Chebychev group delay increases sharply. It will be appreciated that in the limited region 204 where the group delays are of an opposite sign, partial cancellation of the group delay characteristics can be achieved thereby effectively extending the region 206 extending from low frequencies up to approximately 2�105 radians per second where the group delays are essentially invariant with respect to frequency to an increased upper frequency of 106 radians per second.
[0075]FIG. 4 schematically illustrates the magnitude response for the inverse Chebychev and Chebychev filters whose group delays were shown in FIG. 3. It can be seen that the inverse Chebychev filter in this example has a substantially flat magnitude response up to approximately 106 radians per second, and then the magnitude response falls steeply towards a notch occurring at 5�106 radians per second. At this point, the magnitude of the response is suppressed by over 60 dB. The Chebychev filter also has a substantially uniform magnitude response in the pass band, but has a roll over frequency of approximately 2�106 radians per second from where the magnitude falls off rapidly.
[0076]FIG. 5 shows the combined magnitude response of a Chebychev/inverse Chebychev filter using the individual filters shown in FIGS. 3 and 4. It is seen that the combined response 210 is substantially flat up to 106 radians per second and then falls steeply, being approximately 10 dB down by 2�106 radians per second and over 60 dB down by 5�106 radians per second. Furthermore, the group delay can be maintained as substantially constant up to 1�106 radians per second.
[0077] It is appreciated by the person skilled in the art that analog filter design is an immensely complex mathematical exercise. It is, however, also well known that many filter designs have already been analyzed and described in a normalized form such that an engineer can effectively use a "recipe" of a standard form to design a specific filter characteristic. Furthermore, computer aided design packages now also allow for filter characteristics to be accurately depicted. For these reasons, the specifics of the design do not need to be described in detail as sufficient support exists in the prior art to enable the person skilled in the art to implement the filter. However, for the specific filters whose responses are shown in FIGS. 3 to 5, the Pole positions for Inverse Chebychev response were calculated by first calculating the pole positions for Chebychev response and using pole reciprocation.
[0078] Valid poles exist in the negative half of the S-plane
[0079] Position of stopband zero
[0080] The Inverse Chebychev Transfer function used was
[0081] The Pole Positions for solution to Chebychev Polynomial were
[0082] Valid poles exist in the negative half of the S-plane
[0083] The Chebychev Transfer Function used was
[0084] The Transfer Function of Hybrid Filter is the combination of the two individual transfer functions:
X i:=(Hci�Hici)
[0085] Being a hybrid filter, each of the two elements of the filter can be individually adjusted to better tailor the response of the filter to meet the needs of the particular application
[0086] For example, with the Chebychev response, it is possible to adjust the following:
[0087] 1. The cut-off frequency
[0088] 2. The filter order (number of poles)
[0089] 3. The in-band ripple
[0090] For the Inverse Chebychev filter, it is possible to adjust the following:
[0091] 1. The minimum stop-band attenuation
[0092] 2. The maximum tolerable pass-band roll off
[0093] 3. The relative frequency at which the minimum stop-band attenuation is reached
[0094] 4. The filter order
[0095] The filter order can be adjusted by implementing the filter as a cascade of filter stages (i.e. the stages are connected one to another) whereby one or more stages can be switched out of the cascade such that they are bypassed. Thus bypassing a stage reduces the order of the filter.
[0096]FIG. 6 schematically illustrates a dual mode GSM/UMTS transceiver constituting an embodiment of the present invention. The transceiver generally comprises a transmission channel 300 and a reception channel 302. Although represented in simplified form in FIG. 6, the transmission channel 300 actually contains the dual mode transmitter shown in FIG. 1 of the present drawings. In order to simplify the understanding of FIG. 6, those parts of FIG. 6 which are similar to parts shown in FIG. 1 will be given like reference numerals thus, it can be seen that the transmitter receives a frequency synthesized signal from a synthesizer 3, that this synthesized signal is passed through a divide by three frequency divider 9 before being provided to the in-phase and quadrature mixers 15 and 17 of the up-converter. The output of the up-converter is, in a GSM mode supplied to a phase locked loop frequency shifter comprising a phase detector 21, a voltage controlled oscillator 27, a mixer 25 and a band pass filter 23. Thus the operation of these components is as described hereinbefore with reference to FIG. 1. It may be noticed that there are further divide by two frequency dividers 306, 308 and 310 shown in the transmitter schematic, but it will be appreciated that these have little overall effect on the final operation of the transmitter, and in particular that frequency dividers 308 and 310 effectively nullify each other, although they do allow for the mark space ratio of the wave forms to be converted to an ideal 50-50. Similarly, the UMTS path comprises an array of linear amplifiers and a frequency up-converter. The components labeled 37, 39, 41 and 43 as shown in FIG. 1 are schematically represented by the box 320 in FIG. 6.
[0097] It will be appreciated that the receiver section 302 is a simplified representation of FIG. 2. Here the multi-mode fractional frequency multiplier 124 of FIG. 2 is also embodied within the dual fraction synthesizer 3 shown in FIG. 6. It can also clearly be seen that two channels are provided, each having an in-phase and quadrature mixer for frequency down-converting the received signal to the base band. The components 130, 132, 134, 136, 140, 142, 150, 152, 160 and 162 of FIG. 2 are schematically represented by the box 330 in FIG. 6. It is clear that both the transmitter channels share components, both the receiver channels share components, and indeed that the receiver and transmitters share the frequency synthesizer components. This sharing of components allows for cost reductions in the final price of the integrated circuit, and also reduces the overall power consumption of the transceiver compared to implementations where each of these components are provided for their individual functions, and hence effectively duplicated.
[0098] GSM works on a time division duplex system and hence the transmitter and receiver are not operating concurrently. However UMTS operates on full duplex and consequently the transmitter and receiver do operate concurrently. In the UMTS mode it is important to limit the desensitization of the receiver due to interactions with the UMTS transmitter. This is achieved firstly by not integrating the low noise power amplifier with the chip itself, and secondly by limiting the transmitter power at the transmitter output pins. Furthermore, it is important to ensure that the noise level in receive band at the transmit output is adequate. For example, with an external low noise amplifier having 13 dB of gain, the transmit power being limited to +3 dBm at the transmitter output pin and a transmit noise floor in the receive band of −140 dBc/Hz if isolation of 30 dB is obtained between the transmitter and receiver then the impact of the transmitter on receiver sensitivity will be approximately 0.1 dB.
[0099] The architecture shown in FIG. 6 is operable in several modes, the frequency plan for the transceiver may be as follows:
[0100] GSM 850/900 receive mode—the synthesizer frequency is three times the RF frequency.
[0101] GSM 1800/1900 receive mode—the synthesizer frequency is 1.5 times the carrier frequency.
[0102] UMTS receive mode—the synthesizer frequency is 1.5 times the RF carrier frequency.
[0103] GSM 850/900 transmit mode—the synthesizer frequency is 3 times the RF carrier frequency and the intermediate frequency is a � of the RF carrier frequency.
[0104] GSM 1800/1900 transmit mode—the synthesizer frequency is 1.5 times the RF carrier frequency and the intermediate frequency is � of the RF carrier frequency.
[0105] UMTS transmit mode—the synthesizer frequency is 1.5 times the RF carrier frequency and the intermediate frequency is � of the RF carrier frequency.
[0106]FIG. 7 schematically illustrates a hybrid feed forward and feed back automatic gain control system constituting an embodiment of the present invention. The circuit diagram shows a variable gain amplifier whose output is supplied to the hybrid Chebychev/inverse Chebychev filter, generally indicated 402, which has hereinbefore been described. An output of the hybrid filter 402 is provided to the input of a further variable gain amplifier which is schematically represented as three independently electronically controllable variable gain amplifiers 404, 406 and 408 which together serve to provide a variable gain between zero and 54 dB in one dB steps. An output of the final amplifier 408 is provided as an output 410 from the automatic gain controller.
[0107] The feed forward controller, generally indicated 420, comprises a received signal strength indicator (RSSI) log strip which has an input connected to the output of the hybrid filter 402. The RSSI log strip is used to estimate the signal strength at the output of the hybrid filter. The RSSI log strip 422 produces as an output thereof 424 a voltage which is substantially linearly proportional to the composite power of the signal at the output of the filter expressed in dBm. This output signal is filtered by a low pass filter 426 before being supplied to the analog input 428 of a six bit analog to digital converter 430. The signal at the input 428 of the analog to digital converter 430 is digitized in response to a "start convert" signal and the output of the conversion is supplied to a filter gain logic controller 432. The filter gain logic controller has two outputs, one of which is supplied to a register 434 for controlling the gain of the variable gain amplifier 400, whilst the other output is supplied as a 6 bit word to a 6 bit updown counter 440. Thus, the counter can be loaded with the output of the filter gain logic controller 432.
[0108] The signal in a UMTS receiver is a composite of the wanted signal, noise and any residual interfering signals. This composite signal appearing at the output of the hybrid filter 402 is digitized to produce a digital word that has the characteristic of "A" dB per bit, where A represents an arbitrary number. This control word is used to set the gain of the variable gain amplifiers. The variable gain amplifiers are designed to have a gain reduction characteristic of "A" dB per bit. As such, if the signal level into the receiver increases by 5 A dB, then the digitized control word will also increase by 5. This in turn will result in the reduction of the gain of the variable gain amplifiers 404, 406 and 408 by a composite gain amounting to 5A dB. Thus the signal level at the output of the variable gain controller 410 is kept substantially constant. Because the approach described so far uses feed forward techniques, there are no band-width implications that might affect a feed back system. Thus, it is possible to rapidly set up gain for the automatic gain controller for example when switching modes of operation or channels. Having rapidly acquired the composite signal level and setting up an initial gain, further gain control is performed by a feedback scheme.
[0109] The feedback controller, generally indicated 450, comprises a rectifier 452 connected to the output of amplifier 408 in order to deduce a rectified signal representing the signal power at the output of the amplifier 408. The signal from the rectifier 452 is low pass filtered by a filter 454 before being supplied to the inputs of a window comparator 456 which, as recognized by the person skilled in the art, compares the signal at the input therein with high and low thresholds defining a window and produces an output 458 which is indicative of whether the signal is below the window threshold or above the window threshold. The signal 458 is provided to a count direction control input (up/down input) of the counter 440. As shown in FIG. 7, the window comparator 456 is also configured to provide an output which indicates when the input thereto is within the bounds defining the window, and this output is sent to an AND gate 460 which serves to gate the provision of a clock signal to the counter 440. Thus, when the output 410 is within the power band defined by the window comparator 456, the counter 440 is inhibited from receiving its clock signal. The clock signal 462 is also ANDed with an "enable feedback" signal at an AND gate 464 which gives overall control of whether the feedback loop should operate or not. The output of the AND gate 464 is provided to an input of the AND gate 460, the output which is connected to the clock pin of the counter 440. The output of the counter 440 is provided to a gain decoder 470 which in turn sets the gains of the amplifiers 404, 406, and 408.
[0110] In use, the signal level detector and window comparator is used to ensure that the composite signal level and the amplifier outputs is kept within a narrow range, for example +/−0.5 dB. If the composite signal level is above the threshold of the window comparator, the up/down counter is enabled and the gain is adjusted on every clock cycle. As such, the clock sets the time constant of the feedback loop. If the composite signal level is below the window comparator threshold, then the up/down counter is also enabled, but this time counts in the opposite direction. As a consequence, the feedback loop will act to always ensure that the composite signal level is tightly controlled and adjusted at a rate determined by the frequency of the clock 462.
[0111] Referring to FIG. 2, it should be noted that every time a gain control adjustment is made or a offset correction is made, this step change can result in a transient DC offset appearing at the output of the filter. The DC offsets could be removed by a high pass filter, but for a truly generic receiver it is better that the DC offset correction should be performed in the digital domain. Thus at each gain change a new DC offset is estimated and the estimate is supplied to the converters 134 and 136 such that a correction is added at the summers 130 and 132. This said, the transient occurring as a result of gain change still has an unwanted effect of the low pass filters 140 and 150. This transient decays in time, but during the settling time of the filter the homodyne receiver is effectively blinded. This is because the conversion range of the analog to digital converter will necessarily be limited, and the offset may cause the converter to have to convert outside its nominal operating range.
[0112] Given that the receiver is effectively non-functional during this transient period, the inventor has realized that it is permissible to change the filter characteristics during the short period in order to allow for a more rapid settling time. Thus, when a change in gain or offset is implemented, the high pass filter is simultaneously, or near simultaneously set to a wide bandwidth such that the DC transient will quickly settle. The settling time can be estimated from known characteristics of the filter. After the settling time, the filter is automatically switched back to the nominal required setting for its proper operation. The filter can be under the control of a timer, for example implemented as a monostable, which alters the filter characteristics for a brief but well defined period. This technique ensures the fastest possible receiver settling time whilst at the same time minimizing the amount of wanted modulation energy that might be removed by the high pass filter. A typical ratio between the two bandwidth settings might be in the order of 10 to 1, although this is only a non-limiting example and other ratios may be chosen by the design. The implementation of this technique is not dependent on the filter technology. Thus the filter might be implemented as a switched capacitor filter, a switched bandwidth active R-C filter, gyrator- capacitor filter and so on. The specific implementation of the filter is within the knowledge of the person skilled in the art.
[0113] It is thus possible to provide a multi mode receiver and transceiver which are particularly suited for use in mobile telephony.
|Cited Patent
|Filing date
|Publication date
|May 4, 1936
|Mar 28, 1939
|American Box Board Co
|Title not available
|Title not available
|Title not available
|Title not available
|Citing Patent
|Filing date
|Publication date
|Nov 19, 2002
|Jul 11, 2006
|Sony International (Europe) Gmbh
|Digital controlled AGC
|Apr 13, 2004
|Jun 12, 2007
|Skyworks Solutions, Inc.
|Direct current offset correction systems and methods
|Apr 8, 2005
|Mar 23, 2010
|Infineon Technologies Ag
|Transceiver circuit and method for providing local oscillator signals in a transceiver circuit
|Nov 13, 2007
|May 17, 2011
|Provigent Ltd.
|Multi-mode baseband-IF converter
|Dec 27, 2007
|Aug 2, 2011
|Provigent Ltd
|Integrated RF-IF converter
|Feb 27, 2011
|Mar 26, 2013
|Provigent Ltd.
|Carrier recovery in re-modulation communication systems
|Sep 19, 2010
|May 20, 2014
|Zte Corporation
|Device and equipment for four-frequency transceiving of global system for mobile communication
|Feb 22, 2012
|Jul 8, 2014
|Qualcomm Incorporated
|Dynamic receiver switching
|Mar 29, 2011
|Dec 2, 2014
|Huawei Technologies Co., Ltd.
|Communication signal transmission method, device and system
|Mar 14, 2013
|Mar 31, 2015
|Qualcomm, Incorporated
|Reusing a single-chip carrier aggregation receiver to support non-cellular diversity
|Nov 18, 2004
|May 5, 2015
|Qualcomm Incorporated
|Low-power wireless diversity receiver with multiple receive paths
|Aug 13, 2012
|Aug 25, 2015
|Qualcomm Incorporated
|Receiver for imbalanced carriers
|Apr 13, 2004
|Oct 13, 2005
|Bala Ramachandran
|Direct current offset correction systems and methods
|Apr 8, 2005
|Oct 27, 2005
|Zdravko Boos
|Transceiver circuit and method for providing local oscillator signals in a transceiver circuit
|Nov 18, 2004
|Jan 12, 2006
|Persico Charles J
|Low-power wireless diversity receiver with multiple receive paths
|Apr 25, 2006
|Dec 28, 2006
|Matsushita Electric Industrial Co., Ltd.
|Wireless transmission apparatus, polar modulation transmission apparatus, and wireless communication apparatus
|Apr 12, 2005
|Jun 27, 2012
|Direct current offset correction systems and methods
|Apr 12, 2005
|Feb 22, 2007
|Skyworks Solutions Inc
|Direct current offset correction systems and methods
|Jul 15, 2008
|May 22, 2009
|Amir Eliaz
|Multi-mode baseband-if converter
|U.S. Classification
|455/306, 455/307
|International Classification
|Cooperative Classification
|European Classification
|Dec 30, 2002
Owner name: ANALOG DEVICES, INC., MASSACHUSETTS
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:ATKINSON, SIMON;BIRK, PALLE;HO, STACY;AND OTHERS;REEL/FRAME:013632/0887;SIGNING DATES FROM 20020829 TO 20020913
|Feb 26, 2008
Owner name: MEDIATEK, INC., TAIWAN
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:ANALOG DEVICES, INC.;REEL/FRAME:020555/0404
Effective date: 20080129
|May 6, 2011
|Fee payment
Year of fee payment: 4
|May 6, 2015
|Fee payment
Year of fee payment: 8


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Purse Cake
- Uploaded By nanda_129
- 2011-02-08 00:40:55
This is my 8th fondant cake. Also the first time trying to make anything other than a circle or rectangle cake. It was made for my friend's 24th surprise birthday party. I made the purse by cutting the bottom and top off of a double stacked 9 in round.
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Following the recent failed motion to reclassify Elizabethtown as a second class city, the issue is again making headlines. Councilman Steve Atcher's motion, seconded by Councilman Ron Thomas, was struck down by the city council by a 4-2 vote. The time for clearing and cleaning up discrepancy and disagreement regarding classification is long overdue.
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TAMPA, FLA. (AP) - Yankees reliever Joba Chamberlain dislocated his right ankle while playing with his son at a local spot that had a trampoline, jeopardizing his immediate future after yet another odd misstep for New York's bullpen at spring training.
There was no timetable for Chamberlain's return. The team did not say whether the 26-year-old pitcher was using the trampoline equipment when he was injured Thursday.
The accident at a play area came two weeks after All-Star setup man David Robertson hurt himself moving boxes at home.
Yankees general manager Brian Cashman said Friday that Chamberlain had surgery and would be hospitalized at least a few days. The 6-foot-2, 240-pound righty was working his way back from elbow ligament replacement surgery and wasn't expected to return until June or July.
Asked Friday if this could threaten Chamberlain's career, Cashman said: "I'm not in position to say. Right now it's too early for that. He's in very good hands. He's a healer. He's a tough guy."
Bone broke through the skin during the dislocation. Chamberlain was scheduled for an MRI exam and CT scan Friday.
"My guess is he landed funny," Yankees manager Joe Girardi said.
Girardi said he spent about 30 minutes with Chamberlain at the hospital Friday morning that both of them were "a little emotional."
"I wanted to see how he was doing. You know it's crushing. I just told him, we're going to be here for him, we're going to get you through this and we're going to get you back on the mound. But you're going to go through some difficult times," Girardi said.
"You can only look forward. You've got to look forward. You can't look at `what if?'" he said. "You can see the disappointment, there's no doubt that."
Earlier this month, Robertson stumbled on the stairs of his home in St. Petersburg while moving empty boxes for recycling. The Yankees' fears of a serious injury were abated when Robertson was diagnosed with a bone bruise.
And once it became clear Robertson's injury was minor, his teammates let him have it. Among those in the clubhouse weighing in with sarcastic cracks about carrying boxes was Chamberlain himself. Chamberlain often is like a big kid himself, joking with teammates and playing around.
But there was little humor coming out of the Yankees' camp Friday. The mood in the clubhouse was somber, and Cashman seemed shaken as he met with reporters. He even acknowledged at the end of the media session that he was rambling.
"He's facing a lot right now," Cashman said. "I can't tell you, really, anything more than something unfortunate happened. We're in the very early information side of this thing."
In January, Chamberlain agreed to a one-year contract for $1,675,000, up from $1.4 million last year. The deal was not guaranteed. Cashman said Friday it's not the right time to talk about Chamberlain's contract status.


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As of Friday, July 19, 2013
© Copyright 2015 Gwinnett Daily Post
If basketball is Lou Williams' No. 1 pursuit, then music is 1A.
He has released a handful of songs in recent years, though that has slowed down a bit lately. More music is on the way, but when it will become public has yet to be determined.
"I've been doing music since before basketball," the Atlanta Hawks guard and South Gwinnett grad said. "I always kept it to myself. It was a hobby. But it got to the point where we were spending so much time and money and effort, bringing in real artists who make money from music, and they said, 'Listen man, we're not going to help you if you're not going to release it.'
"So we started to kick out a little music and we realized people were interested in it. Now we're trying to figure out a way to put it out and I can still keep it to myself. It's a fine balance. We try to sneak little things out. Some of my real fans know where to find the music. Everybody on the outside looking in, they kind of have to wait until we tell them."
A quick search on YouTube will lead to some of Williams' efforts as a rapper.
The releases include "I Want It All," a collaboration with Meek Mill and "Break From Myself" with K. Michelle. He also joins Meek Mill and 2 Chainz on "Problem." Other credits that are easy to locate online are "Imma Boss-Freestyle" and "Slow It Down."
That's just a brief glimpse into the high-scoring guard's music career.
"One of my good friends started his own label and we've got three acts signed," Williams said. " I help him on the outside because I love music. I look forward to seeing what happens with that."
As for his own music?
"I have over 200 songs recorded, so any time I want to put something out there it's already done," Williams said.
More like this story
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- Rough homecoming for Meeks in Lakers loss ( December 17, 2013 )
- Norcross' Meeks returns to boost surging Detroit Pistons ( January 20, 2015 )
- Norcross grad Jodie Meeks signs with Detroit Pistons ( July 14, 2014 )
- Norcross' Meeks inherits athletic talent, thrives with a new game ( September 10, 2013 )


text:
Hello all,
I just recently switched from windows vista to 64 bit ubuntu 10.10. I'm running it on a R400 thinkpad with 3GB of memory, and integrated intel graphics. I've been very happy with things except the fact that the mouse is very choppy and jumpy. If I start on one side of the screen and smoothly move to the other, the mouse will frequently pause along this track, and "catch up" to where it should be. This happens maybe 2/second. I've tried my trackpad, USB mouse, and the little red dot that lenovo loves.
Any thoughts? I used lshw to show my chipset and saw that there are two entries for the graphics card - one is showing up as UNCLAIMED. There's also a communication module UNCLAIMED.
I'm a newbie - any help'd be great. Thanks.
Since installing 10.10 on my Acer Aspire 6530G I can't access the internet when connected with a wired connection and my wireless connection is disabled and can't be enabled.
Can anyone help.
For the second time in a year I have upgraded to a new Ubuntu and lost internet access! And we expect people to drop Windows and flock to Linux??!! I don't think so.
Last time it was my wireless dongle which didn't work.
This time 10:10 it has switched off my wireless and won't let me switch it on again and when I connect by wire it won't connect to the internet!!!
So I have no chance of getting it fixed!!
I find myself wanting to move to Linux completely but I am thwarted at every upgrade!!
Come on guys surely we can keep the things which were working working when there is an upgrade otherwise it's not an upgrade - just another embarrassment.
I'm so glad the people whom I have encouraged to try Linux have not done so - or they would have been put off forever.
Sent from my Windows 7 desktop which seems to work impeccably. Which is even more annoying.
I was trying to get my new Panasonic 50" plasma to work as a monitor for an Ubuntu 10.10 installation.
My Gforce 6200 256mb has both VGA and DVI ports out back.
I had the VGA connected to an LCD and the DVI connected via DVI to HDMI cable to the Plasma.
I'm installing 10.10 as the only OS on an older P4 computer. Just 1 gig or RAM and a 40 gig HD. I'm installing from a CD iso file. It has gotten as far as asking for my name and a user name and password, it seems to load most of the files and the progress bar is nearing the end, but just stops. I've no idea what to do. It's my first experience with Ubuntu.
In windows you want to see computer and system information there are many methods for Exp:-To see Microsoft System Information, use either of the following methods:
• Click Start, point to Programs, point to Accessories, point to System Tools, and then click System Information.
• Click Start, click Run, type msinfo32.exe in the Open box, and then click OK.
In the same way in Ubuntu system you want to see computer and system information in Graphical Mode you have to install Sysinfo
What is Sysinfo: - Sysinfo is a graphical tool that is able to display some hardware and software information about the computer it is run on.
It is able to recognize information about:
. System (Linux distribution release, versions of GNOME, Kernel, gcc and Xorg and hostname);
. CPU (vendor identification, model name, frequency, level2 cache, bogomips, model numbers and Flags);
. Memory(total system RAM, free memory, swap space total and free cached, active, inactive memory);
Is there any way to make magic jack work on ubuntu 10.10?
In my first article that is posted at 29.10.2010 "Installing Ubuntu 10.10 on a Windows 7 System (Dual booting) with Radeon X300/X550/X1050 SERIES Graphics Card". I got most of email in that most of the people are asked me to give step by step Installation method for Windows 7 and Ubuntu 10.10 in dual booting. So I am trying to give you to installation method for both Operating Systems. I hope it will help to you for easy installation for Windows 7 and Ubuntu 10.10 in Dual booting method.
First you have to download avast anti virus software from avast website
now you will see avast web page called avast Linux home edition
you will see a Note: the program will not work with out a valid license key. To get your key places use the registration form.
You have to click on registration form now you will see a new page called "Register for your free avast 1 year license" in the you have to give full details information to register for free license you will get key to your mail.
Now you have go to avast Linux Edition (DEB Package)
now you will see opening avast 4 workstation_1.3.0-2_i386.deb box
you have to select
(.) open with "Ubuntu software Center (Default)"
press {OK} button
after downloading is over. You will see a box called Ubuntu software Center in that you see Right side a small box called Install
just press that Install Button
In Ubuntu 10.10 by default web browser is Mozilla fire fox web browse is using for internet browsing.
If you want to read Telugu and other news paper first you have go to System ---> Administration---> Language Support --> and click it
you will see a box called Language & Text box
It will update automatically when you open Language Support
after update is over you have to go ---> Install/Remove Languages ---> and press it
you will see a new box called installed languages and you can fined 145 languages list
for Exp:- I choose Telugu now you can see four options in the bottom of the box
under components:
1.Translations 2. Spell cheking and writing aid 3.Input methods 4.Extra fonts
click all the boxes
and now press apply changes button
after changes is over now you have to install padma plugging for Fire Fox web browser. For
that you have to open Mozilla fire fox web browser and you go to goole and type padma plunging
In my first article that is posted at 29.10.2010 "Installing Ubuntu 10.10 on a Windows 7 System (Dual booting) with Radeon X300/X550/X1050 SERIES Graphics Card". I got most of email in that most of the people are asked me to give step by step Installation method for Windows 7 and Ubuntu 10.10 in dual booting. So I am trying to give you to installation method for both Operating Systems. I hope it will help to you for easy installation for Windows 7 and Ubuntu 10.10 in Dual booting method.
I have installed Windows 7 and Ubuntu 10.10 on HP dx 7200 micro towers.
System Information :-
Operating System: Windows 7 Ultimate 32-bit (6.1, Build 7201) (7201.winmain_win7ids.090601-1516)
Language: English (Regional Setting: English)
System Manufacturer: Hewlett-Packard
System Model: HP Compaq dx7200 Micro tower
BIOS: Default System BIOS
Processor: Intel(R) Pentium(R) 4 CPU 3.20GHz (2 CPUs), ~3.2GHz
Memory: 4096MB RAM
Available OS Memory: 3584MB RAM
Display Devices
It still functioning well when i used it last nite i am very sure that i quick it properly. But today when i on my pc it showed "INSTALL PROBLEM" ar the top of right hand site corner. It is like that:
The configuration defaults for Gnome Power Manager have not been installed correctly. Please contact your computer administrator.
At the same time, at the to top of left hand site corner it said that:
An error occurred while loading or saving configuration information for evolution-alarm-notify. Some of your configurations setting may not work properly.
That all it show out when i on my laktop and not even have the chance to type my password and get into the system yet.
So what i going to do to fix this problem as i am totally new in Ubuntu 10.04. I am fresh user. I love the simple and speed of Ubuntu and dont want to change to window now.
Please help me on this problem if you guys know how to fix this. Thanks so much.
I have made a tutorial on how to make your panels, tabs and menus transparent. just visit my site: http://jechem.blogspot.com/2010/11/making-panels-tabs-and-menus.html. There are pictures to help you on the procedures.
For no obvious reaason I have lost my background. If I go to change background and pick a background, it comes up, but after a few minutes disappears.
Can anyone tell me why and how to cure this problem.
I just installed ubuntu 10.10 on my laptop Dell Inspiron 1525. Wireless internet is not working. I installed wicd network manager and I am able to see the available wireless networks. My wireless connection is encrypted. I have tried all encrypted options with the key but no avail. It says "Cannot obtain an IP address" after validating authentication. Kindly help.
============ lspci ============
00:00.0 Host bridge [0600]: Intel Corporation Mobile PM965/GM965/GL960 Memory Controller Hub [8086:2a00] (rev 0c)
Subsystem: Dell Device [1028:022f]
Kernel driver in use: agpgart-intel
Kernel modules: intel-agp
00:02.0 VGA compatible controller [0300]: Intel Corporation Mobile GM965/GL960 Integrated Graphics Controller [8086:2a02] (rev 0c)
Subsystem: Dell Device [1028:022f]
Kernel driver in use: i915
Kernel modules: i915
00:02.1 Display controller [0380]: Intel Corporation Mobile GM965/GL960 Integrated Graphics Controller [8086:2a03] (rev 0c)


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September 15, 2009
Lucky, 4 yr. old Pit Bull Boxer Mix
Java J's in the North Loop, North Loop Dog Park, Minnehaha Dog Park
I found the Boxer Group first, but found they don't allow mixed dogs to join. Then I found the Bully Lovers which is a much better mix!
I have a 4 yr. old pit-boxer mix who loves to play! And it's always nice to find other Bully Breeds who play the same way as him, and meet other Bully Lovers like me!
This group provides a great opportunity to get my dog out and socialize him, without having people pre-judge him based on how he looks, or think that he's mean if he play a little rough. This group always has a lot of events going on, but there is no pressure to participate or not, which I really like. I can be as involved a I want to be, but being more involved has definitely been a lot more fun!
Meetup members, Log in
By clicking "Sign up" or "Sign up using Facebook", you confirm that you accept our Terms of Service & Privacy Policy


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Extended Stay Deluxe Jackson
No prices found through our partners. Please contact the business directly or check some of our recommended alternatives.
TripAdvisor Reviews Extended Stay Deluxe Jackson
Travel Blogs from Jackson
On the Way to Canton, Texas
... a detour through little towns on US 80 and still arrived in good time and daylight, but tired out. Not as young as we used to be. I'll get Randy's face shot tomorrow for everyone to watch his hair grow.
Bedding down tonight so we can have a full day at the market tomorrow. Dogs are sleeping again, but doing well.
God Bless and see you all tomorrow!
Randy and Betty
Capital of Mississippi
... thought she was in then noticed his wedding ring. Must of thought this fellow with cigarettes and a brand new Chevy Impala had some money for her next hit. Sorry love - missed out here.
A nice cheap place to stay and was clean and another comfortable bed. Even the cheap accommodation has good beds and ...
Travel Day
We had an uneventful trip from Shreveport to Edwards, MS. It's between Vicksburg and Jackson. The skies were cloudy and the traffic was light.
The campground we stayed in overnight was interesting. It's very rural – as in going to the end of a private country road and there you are. It had a lovely pond for fishing. The office was a small weathered wood structure with a camp store with a little bit of ...
Trip 5: Tuscaloosa to Jackson
... girl and god forbid they try to take me out.
And that's that. I'm not wandering around Jackson alone at night. Instead, I'm hanging at Sneaky Beans writing this for you to read until Danny gets off work :)
After he got off work, we stopped at his friend Jordan's for a little bit before heading to his friend Don's place where we're staying for the night. Yep, I opted to surf for one more night. And now I'm going to bed. Tomorrow we're off to New ...
Canton, MS
... can enjoy not only a scenic drive but also hiking, biking, horseback riding, and camping. Will have to come back some day and do rest of parkway. We drove 86 miles from Natchez, MS to Clinton, MS.
One night stop over on way to Memphis, ...
Other places to stay in Jackson
Drury Inn & Suites Jackson225 Drury Lane, Jackson | 3 star hotelfrom $95
Comfort Suites Jackson/Cape Girardeau2904 Old Orchard Road, Jackson | 2 star hotelfrom $106


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Change Location
ACE Fit Share
Whether you're a beginning exerciser who needs help getting started or someone who wants to add some spice to your fitness routine, our ACE Exercise Library offers a variety of movements to choose from. Browse through total-body exercises or movements that target more specific areas of the body. Each comes with a detailed description and photos to help ensure proper form.
By Body Part
By Equipment
Browse Workouts
Exercise Videos
Fit Life Articles
You know that eating more fruits and vegetables is good for you, but it can be daunting to think about cutting out meat and making the switch to a more plant-based diet. The good news: You don't have to give up meat altogether to eat healthier. If you're considering...
Too busy for breakfast? The key to starting your mornings off right is planning a healthy breakfast the night before. Here are some healthy and delicious breakfast options that will help jumpstart your metabolism and fuel your body and brain for the morning.
A strong core is essential for a healthy back and a body that moves well in both sports and everyday life. This 10-minute workout strengthens the muscles of the torso through the use of static-hold exercises coupled with dynamic movements, all of which will challenge these...


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"The card design is super cute! I just wish I would have used a darker pink for the font at the bottom of the card as it's a little hard to read but other than that, I love the simple design and the card quality."
"I liked writing my Baby Shower thank you notes on these. We had an elephant theme-- even though these didn't match our theme exactly, they were suitable for me to send out as replacement for the elephants that we used at the shower. The ink that I used didn't smear at all. Because it's not a card that you open up, I was able to post one at my workplace and give one to my husband to post at his work place in our break rooms for thank you for group notes."
"I am so glad I ordered these! The paper quality is exceptional and the design and quality of the notes are adorable. I will have to order more when I run out!"
"I love how pretty and classy these notes and labels are. The print on the invitation and label is a bit small but easily remedied with increase in font size."
"I loved that there were thank you cards that matched the invitation that I chose, however, I would have preferred to have a picture uploaded with it, and this particular invitation/thank you card set doesn't allow you to have a picture"


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Ice2D Game Engine + Kinetics camera in arcade machine3 years ago News 1 comment
Ice2D Game Engine was build into an Arcade machine with live camera and from a XBOX Kinetics camera and taking live image of players as background inside...
Ice2D™ Game Engine is Royalty free for use with any type of freeware, shareware or commercial game with focus on independent games and tools developers. Ice2D™ is designed to be used for rapid development of multimedia and games in 2D or ISO metric view with some simple 3D Cut scenes available. Features include Fast sprite engine, isometric maps and objects, tweening, particle effects, bitmap fonts, game scene manger, flexible rendering with directX9. Many Source codes examples provided in Vb.net C# for vs.2010 and vb classic / vb6 or other COM enabled languages
A few years back I tampered with using webcams for games in DirectX9. The idea was of course to make a game ala Eye toy games for PlayStation. However grabbing the images and loading them into a direct texture proved to be very slow so i had to give up
Then I was asked about VMR9 and it looked promising in the examples i tried. I started implementing it for Ice2D Game Engine, but couldnt make it work. First, I allocated a device for the VMR9, but quickly found out that it's not possible to move textures directly between 2 directx devices. Then i tried using the Ice2D's device for VMR9 but somehow VMR9 messed up the device so Ice2D would stop rendering. Again, I was back with nothing!
6 month later i started to think that perhaps I needed to make a IDL for directshow so i could build the render graph and use ISampleGrabber. I knew from my test with webcam that the grabber was very fast and after constructing the IDL typelibrary it became must easier to work with.
Final outcome is a fully working video and webcam rendering to a real directX9 texture with good performance and the IceVideo interface also allow you direct access to a BMP32 buffer before it's moved to the directX9 texture. This buffer access makes it possible to program simple color filters and even some webcam motion detection in real time - A real success after a long struggle.
IceVideo will be released in Ice2D Game Engine v2 - Happy New Year!
Ice2D Game Engine was build into an Arcade machine with live camera and from a XBOX Kinetics camera and taking live image of players as background inside...
Magic Speel Book a mini game in the making. Primarily to test new features of the upcomming version 1.90 of Ice2D. IceFX particle effects improved, IceFont...
This is a small game design document template you can use to improve your game design process and as a check list.
No articles were found matching the criteria specified. We suggest you try the article list with no filter applied, to browse all available. Post article and help us achieve our mission of showcasing the best content from all developers.
Latest tweets from @ice2dgameengine
Users report Ice2D game engine runs fine on Window 8 6bit with .NET 2012
Jan 3 2013
Webcam and Video on DIrectX9 Texture with great performance. It's even possible to manipulate the BMP32 buffer before moving to texture!
Dec 11 2012
More Success! Webcam on DirectX9 Texture with super good performance
Dec 8 2012
Succes! Video on real Texture in Ice2D Game engine AND great performance.
Dec 8 2012
Breakthrough on making Video play on real Dx9 Texture. Performance is good. dx9 Texture can be used as sprite or on a mesh object :)
Dec 3 2012
New Forum software now on Ice2D Game Engine Forum T.co
Nov 23 2012
Summer is here - so usually less dev activity and more play. Pip me some nice casual or sim games to try out
Jun 18 2012
Promote Ice 2D Game Engine on your homepage or blog by selecting a button and using the embed code provided (more).


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McDonald'sFebruary 28Fast Food • Madison, United States
Always upsets My stomach
I like life simple
This is a very clean restaurant out of a lot of the subways that I've seen
Very fast, friendly, and accommodating staff
This is the first time ever I've been in Chuck E Cheese's it was a wonderful experience
This is my favorite grocery store
I don't know why this is on my list cuz I don't remember going to this place
I've been going to this Coliseum since I was a little girl. Wonderful experiences
They have all kinds of interesting stuff
It was very nice. Very laid back, clean environment, friendly staff, and smiling faces.
Best Bakery on the North side of Madison.
♥ n Thank you. God bless.
Best place by far. I've never had any issues with any of my cars after they get done fixing it.
I don't like sushi so I'll never step inside here.
It was alright. They started playing good music as they set off the confetti telling people it's time to leave.
Ha ha ha ha gotta love the name lol
This Park had everything. Beautiful.


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The Sea of Memories
by Bush
- Record Label: eOne
- Release Date: Sep 13, 2011
- Band members: Gavin Rossdale, Robin Goodridge, Chris Traynor, Corey Britz
- Summary: The English post-grunge group release their fifth studio album, produced by Bob Rock.
- Record Label: eOne
- Genre(s): Grunge, Pop/Rock, Alternative/Indie Rock, Alternative Pop/Rock, Rock & Roll, Post-Grunge
- More Details and Credits »
Score distribution:
Positive: 1 out of 10
Mixed: 9 out of 10
Negative: 0 out of 10
Sep 30, 2011As a record, this The Sea of Memories is easily the most enjoyable collection of songs released under Bush's name.
Sep 12, 2011The quartet's first record in a decade is a surprisingly vital viva-la-grunge manifesto.
Nov 17, 2011The Sea of Memories will most likely please those few Bush fans who've been hoping for a reunion, but it will not change the minds of those who relegated Bush to nothing more than a disingenuous rip-off of so many more brilliant '90s alterna-rock acts.
Entertainment WeeklyOct 6, 2011The Sea adds exactly zero entries to the totally awesome Bush greatest-hits album that doesn't exist yet. [23 Sep 2011, p.79]
Oct 11, 2011The Sea Of Memories plays like an endless replay of Rossdale's past musical miscues.
Sep 9, 2011It's a mediocre album, and I'm only being hard on you because I sincerely wanted more. Like a pissy parent, I'm not mad at you... I'm disappointed.
UncutNov 23, 2011Bob Rock's big production ladles on the reverb, merely emphasizing hollowness at the core. [Dec 2011, p.81]
Score distribution:
Positive: 1 out of 4
Mixed: 2 out of 4
Negative: 1 out of 4
Oct 3, 2011I enjoyed this album as a whole ,but i can not find one track that is going to stick in my head 10 years from now . I think they lost some ofI enjoyed this album as a whole ,but i can not find one track that is going to stick in my head 10 years from now . I think they lost some of the hunger in the early albums and replaced it with well written songs ,that are well thought out but not amazing . All in all if you like bush ,you should enjoy this .… Expand
Nov 3, 2011Overproduced album with none of the rawness that made Bush's first two albums some of the best guitar rock of the mid-to-late 90's. Bob Rock'sOverproduced album with none of the rawness that made Bush's first two albums some of the best guitar rock of the mid-to-late 90's. Bob Rock's production has sucked the soul out of these songs. It essentially sounds more like a follow up to Rossdale's 'Wanderlust' album than a Bush album. He desperately needs Nigel Pulsford back and desperately needs a good producer. Another study in how a woman with a four letter name (Yoko/John, Etty/Jane's Addiction, Gwen/Gavin) softened their man to the point of artistic collapse.… Expand
Nov 7, 2011As a whole I think it's better than their last two releases. The front end is stronger than the back end but it's medium quality is prettyAs a whole I think it's better than their last two releases. The front end is stronger than the back end but it's medium quality is pretty consistant. It's nothing special.… Expand
Sep 29, 2011What I wouldn't give for the days of even Golden State. Bush desperately needs their original bassist and lead guitarist back.
|Sticky Fingers [Deluxe Edition] - The Rolling Stones
|You Can Make Me Dance, Sing or Anything: 1970-1975 [Box Set] - Faces
|Miles Davis at Newport: 1955-1975 The Bootleg Series, Vol. 4 - Miles Davis
|Elitism for the People 1975-1978 [Box Set] - Pere Ubu
|No Closer to Heaven - The Wonder Years
|M3LL155X [EP] - FKA Twigs
|Live at the Fillmore East: October 4th & 5th, 1968 [Box Set] - Sly & the Family Stone
|Radio Static High - Hey Colossus
|That's the Spirit - Bring Me the Horizon
|From Kinshasa - Mbongwana Star
|The RCA Victor and T-Neck Album Masters: 1959-1983 [Box Set] - The Isley Brothers
|Have You in My Wilderness - Julia Holter
|John Howard & the Night Mail - John Howard & The Night Mail
|Choose Your Weapon - Hiatus Kaiyote
|Summertime '06 - Vince Staples
|Something More Than Free - Jason Isbell
|Remembering Mountains: Unheard Songs By Karen Dalton - Various Artists
|The Blade - Ashley Monroe
|The Longest River - Olivia Chaney


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President Nixon set the stage yesterday for a major constitutional confrontation by refusing to turn over presidential tape recordings to either Senate Watergate committee or to Special Prosecutor Archibald Cox.
Cox immediately served a subpoena for the tapes on presidential counsel J. Fred Buzhart, who must respond in federal court by Thursday. The Senate Committee followed suit, serving two subpoenas on another presidential lawyer, Leonard Garment.


text: My gf and I were walking in a 300 acre park and we watched a girl fingering her pussy. My gf started getting hot and was rubbing against me, then moved in front of me so she could rub her ass on my hard and pulled my arms around so I could squeeze her nipples. She wasn't wearing any panties, so she just lifted her skirt a bit and she got my dick in her. She started making noise and the girl who was masturbating heard her, and came over to see us fucking... she joined us.


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Pep Hiv
Apr 22, 2012
Hello dear Doctors, I wanted to know which are the differences between the occupational and non occupational HIV PEP. Could the nPEP be less effective? I also wanted to ask why sometimes two medicines are prescribed while other times three or even four different kind of medicines are suggested to take. Thank you very much for your answers
Response from Dr. Young
Hello and thanks for posting.
There are different US guidelines for evaluation and treatment for non-occupational HIV exposure (nPEP) and for post-occupational-exposure prophylaxis (PEP). This is mostly a historical artifact, rather than any attempt to compare the effectiveness of one strategy over the other. There's no reason to think that nPEP is any less effective than PEP.
Also, while the two guidelines recommend a range of therapies, since much of the scientific studies that are the basis of the recommendations is older, many experienced providers may use different regimens.
Many of the details to your questions can be found by looking through the nPEP and PEP guidelines.
Be well, BY
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Follow me on insta olivierbnw /oliviercolours Admin picturetokeep_bnw & france_photolovers 📱Samsung S6 📷 panasonic DMC
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Follow @DaytimeRoyalty
|Viewing Single Post From: Days Weekly Preview (5/5/2014)
|May 3 2014, 10:04 PM
"I love you, Aiden. I love you." "I love you."
I would LOVE to get Rachel Melvin back, even if only for a 13 week stint. It would be fun to watch Ciara & Chelsea interact as well as find out what Chelsea really thinks of her father's extended absense (& "deep cover mission").
|Days Weekly Preview (5/5/2014) · DAYS: News, Spoilers & Discussion


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GAO studies have shown increasing use of reverse auctions, including some instances where they weren't used very effectively.
OPM is partnering with CSID to try to manage the fallout from a massive breach of some 4 million federal personnel records.
News and notes from around the federal IT community.
U.S. officials reportedly suspect China's involvement in the hack.
Sorting out the alphabet soup of federal acquisition options means focusing on what your agency values most.
A glut of acting inspectors general is a threat to effective agency oversight, watchdog groups told senators in a hearing that focused on speeding up the confirmation process.
The HHS acquisition innovator is looking for a vendor to handle a web overhaul for the Office of Population Affairs.
There is inherent tension among the various IT sources for federal buyers, but GSA's Mary Davie says there is plenty of business to go around.
In the wake of a massive breach, the IRS says it can stay one step ahead with more money -- and a special hiring authority.
The goal of the proposed blanket purchase agreement would be to decrease software acquisition cycles to less than four weeks.
The crucial next phase of the $6 billion acquisition vehicle will focus on identity management.
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Oscar Cardozo
Benfica's Paraguayan forward Oscar Cardozo celebrates after scoring... News PhotoBayer Leverkusen,Celebration,Club Soccer,Forward - Athlete,Germany,Horizontal,Leverkusen,Match - Sport,North Rhine Westphalia,Oscar Cardozo,Paraguay,S.L. Benfica,Scoring,Soccer,Soccer Player,Sport,Striker,UEFA Europa LeaguePhotographer ODD ANDERSENCollection: AFP 2013 AFPBenfica's Paraguayan forward Oscar Cardozo (L) celebrates after scoring during the UEFA Europa League football match Bayer 04 Leverkusen vs SL Benfica on February 14, 2013 in Leverkusen, western Germany. AFP PHOTO / ODD ANDERSEN (Photo credit should read ODD ANDERSEN/AFP/Getty Images)