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Performance Investigation of Switched Reluctance Motor Driven by Quasi-Z-Source Integrated Multiport Converter with Different Switching Algorithms

: Switched reluctance machines (SRMs) have received increasing attention for their many potential uses, such as for wind power and electric vehicle (EV) drive systems. The Quasi-Z-source Integrated Multiport Converter (QZIMPC) was recently introduced to improve the reliability of the SRM driver through small capacitance values. It is not possible, however, to simultaneously energize and deenergize two SRM phases in QZIMPC. This phenomenon can signiﬁcantly increase the commutation period which, in turn, degrades the performance of SRM; in addition, this causes high-voltage ripples on the converter’s capacitors. Two switching algorithms are introduced and applied in this paper, and their performance with SRM is investigated in terms of torque ripple and peak phase current. The algorithms are based on prioritizing the control command in the on-going and off-going phases to fulﬁll the required load torque, as well as to accelerate the commutation process where possible. This is achieved without the interference of high-level controllers, which include speed controllers and/or torque ripple minimization. Through the simulation results, a comparison between the two switching algorithms is presented to determine their potential to improve the SRM drive system’s performance.


Introduction
Switched reluctance machines (SRMs) are gaining attention for their utility in many applications, including renewable energy systems such as wind, wave and tidal energy systems, and electric vehicle (EV) drive systems [1][2][3][4]. This is due to their simple structure: both the stator and rotor are formed from salient poles, and neither permanent magnets nor conductors are required on the rotor. Furthermore, SRMs use the concentrated type of stator winding. This simple structure offers many advantages, including a low manufacturing cost, rapid acceleration, robust operation under high-speed and high-temperature conditions, and fault-tolerant capability [3][4][5][6].
The torque produced by the SRM phase is expressed in Equation (1) [3], where i ph is the phase current, L is the phase inductance, and θ is the stator phase angle with respect to the rotor. According to (1), the phase torque is positive during the positive slope of the phase inductance, negative during the negative slope of inductance, and zero during the constant inductance intervals. Therefore, to avoid motor operation under negative torque production, the off-going phase should be completely demagnetized as fast as possible before reaching the inductance negative slope region. The operation of SRM phases consists of three modes: magnetization, regenerative demagnetization, and freewheeling modes. Ideally, each phase should conduct a rectangular current waveform, such that when one phase is demagnetized, excitation in another phase begins. However, due to the non-linear inductance of SRM phases and the rotational back-induced Electromotive Force (EMF), phase currents do not instantaneously rise or decay [3]. This commutation behavior is illustrated in Figure 1. Finite element method (FEM) simulations are usually adopted to analyze and optimize the SRM performance [7].  In addition, due to the large amount of energy transfer between the input power source and SRM during commutation, a large filter capacitor is necessary to balance the difference in instantaneous power. Long periods of commutation can also significantly limit the speed range of SRM and decrease its torque productivity [8][9][10][11].
To reduce the torque ripple, current overlapping of two SRM phases is usually adopted [12,13]. This overlapping can be achieved through the simultaneous operation of two adjacent SRM phases using one of the following options: • Simultaneous magnetization of the on-going phase and regenerative demagnetization for the off-going phase.

•
Simultaneous magnetization of the on-going phase and freewheeling of the off-going phase.
The first option is more desirable, as it can significantly reduce the commutation period; this becomes more critical at high speeds to produce the load torque required.
To shape the SRM phase currents properly, the SRM drive system consists of a power converter and a suitable control algorithm to control the phase current amount along with the rise and fall times; a schematic for an SRM-based drive system is shown in Figure 3. Thus, the overall performance of the SRM drive system is particularly affected by the power converter topologies. Asymmetric H-bridge converters are usually adopted in SRM drive systems [3,14]. This topology requires 2 × n switches and 2 × n diodes for a n-phase SRM. The high number of semiconductors increases the overall cost and reduces drive efficiency. While shared switch converters can offer a low number of semiconductors, they are only applicable for SRM with an even number of phases [15]. In addition, due to the large amount of energy transfer between the input power source and SRM during commutation, a large filter capacitor is necessary to balance the difference in instantaneous power. Long periods of commutation can also significantly limit the speed range of SRM and decrease its torque productivity [8][9][10][11].
To reduce the torque ripple, current overlapping of two SRM phases is usually adopted [12,13]. This overlapping can be achieved through the simultaneous operation of two adjacent SRM phases using one of the following options:

•
Simultaneous magnetization of the on-going phase and regenerative demagnetization for the off-going phase.

•
Simultaneous magnetization of the on-going phase and freewheeling of the off-going phase.
The first option is more desirable, as it can significantly reduce the commutation period; this becomes more critical at high speeds to produce the load torque required.
To shape the SRM phase currents properly, the SRM drive system consists of a power converter and a suitable control algorithm to control the phase current amount along with the rise and fall times; a schematic for an SRM-based drive system is shown in Figure 3. Thus, the overall performance of the SRM drive system is particularly affected by the power converter topologies. Asymmetric H-bridge converters are usually adopted in SRM drive systems [3,14]. This topology requires 2 × n switches and 2 × n diodes for a n-phase SRM. The high number of semiconductors increases the overall cost and reduces drive efficiency. While shared switch converters can offer a low number of semiconductors, they are only applicable for SRM with an even number of phases [15]. Star-connected converter topology, shown in Figure 4a, can reduce the number of switches and diodes to n + 1 of each. In addition, the smaller quantity of wires decreases the cost of maintenance and manufacturing [16,17]. In this converter, an asymmetrical leg is connected to each SRM phase. One common asymmetrical leg is also connected to the star connection point of the inverter. Sc and Dc are the switch and diode of this common leg, respectively. For an arbitrary phase i, magnetization can be achieved through S c and S i ; on the other hand, demagnetization can be achieved through D i and Dc. For freewheeling, both (Sc and Di) or (Si and Dc) can be utilized to realize this mode. Although this configuration uses a low number of semiconductors and is applicable for use with an SRM having any number of phases, it has the following limitations:

•
The speed range is limited because simultaneous magnetization and demagnetization of two SRM phases cannot be realized.

•
It cannot offer a boosting gain; thus, magnetization and demagnetization are achieved with voltages equal to the source voltage. Therefore, it cannot offer fast magnetization and demagnetization, resulting in low torque productivity from SRM. • A high decoupling capacitor is required to decouple the difference in the instantaneous power. This represents an obstacle to the overall reliability and the commercial competitiveness of SRM drives.
To overcome these limitations, number of converters were derived based on a starconnected configuration, as follows: • C-dump converters were introduced to offer boosting voltage capability [18]. In this converter, the capacitor voltage is usually regulated to offer double the input voltage during demagnetization. Although this offers fast demagnetization for the off-going phase, the torque productivity is still limited due to the low voltage offered during magnetization of the on-going phase. • An integrated multi-port converter (IMPC) is presented in [10] and shown in Figure 4b. In this topology, the SRM phase voltage can be significantly increased through an integrated DC-DC boost converter to the star-connected topology. Compared to the basic star-connected configuration, IMPC needs to replace the diode of the common asymmetric leg with another switch. IMPC can offer two benefits: first, the necessary capacitance can be reduced significantly, decreasing both the cost and size of the drive; second, it can offer high torque productivity, as the magnetization and demagnetization voltages are increased. However, the boosting unit of IMPC increases the voltage stress on the capacitor and semiconductors. • A quasi-Z-source integrated multiport power converter (QZIMPC), shown in Figure 5a, was recently presented in [11]. In this converter, a quasi-Z-source unit is impeded in front of IMPC in place of a single inductor. This maintains the advantages of IMPC while decreasing the voltage rating of the capacitors. Although QZIMPC has benefits compared to the basic star-connected configuration, it cannot offer simultaneous magnetization and demagnetization to two adjacent SRM phases. This phenomenon can significantly increase the commutation period which, in turn, limits the speed range of SRM. The performance of QZIMPC was verified in [11]; the results show that high ripples of the capacitors' voltages and input currents occur when the speed of the SRM is increased. Such ripples can cause severe thermal stress, which results in a significant reduction in the capacitors' lifetime [19,20]. To tackle this limitation, two switching pattern algorithms for QZIMPC are presented in this paper. These control algorithms are based on prioritizing the control command in the on-going and off-going phases to fulfill the necessary load torque, as well as to accelerate the commutation time as much as possible. The algorithms introduced do not interfere with higher level controllers, such as torque sharing functions (TSF), for torque ripple minimization [12]. Following this introduction, the basic operation of QZIMPC topology is described; then, the control system, along with the proposed switching algorithms, is explained. Simulation results are then introduced to verify the feasibility of the proposed algorithms and their effects on the performance of the SRM drive system. Finally, the conclusion is presented.

Topology Description
The quasi-Z-source integrated multiport converter (QZIMPC) is shown in Figure 5a. It consists of a quasi-Z-source unit in front of the basic star-connected configuration. For n-phase SRM, QZIMPC uses two inductors, two small capacitors, only n + 3 switches, and n diodes. In addition, it needs n + 1 cable for wiring. By increasing the capacitors' voltages, the necessary capacitances can be significantly decreased. The magnetization and de-magnetization times can also be decreased, and, therefore, a larger average torque could be obtained. The operation of QZIMPC consists of five modes for each phase. These modes are shown in Figure 5b-f.  Figure 6 shows the control system adopted for the QZIMPC driver. It consists of two loops. The first loop regulates the capacitor voltage and input current using two controllers of G V and G I , respectively; this loop determines the duty cycles of the switch S sh . Accordingly, it determines the shoot-through time of the quasi-Z-source unit. On the other hand, the second control loop regulates the SRM speed using controller G N . According to the load torque and the position of the SRM phases, the output of G N generates the reference values of the SRM phase currents (I ref ). The PI controller, with general expression in Equation (2), is used to implement G V , G I , and G N . According to the state of S sh (determined by the first loop), along with the reference values of the SRM phase currents (determined by the second loop), the proposed switching algorithm decides the switching states of the remaining switches (S 1 -S 5 ).    The on-going and off-going phases are identified according to the reference values of SRM phase currents. They are denoted as phase k and k-1, respectively.

2.
According to the state of the switch S sh , it can be determined whether or not the quasi-Z-source unit is in the shoot-through mode. If S sh is OFF (shoot-through mode), then the switches S u and S d are switched ON. In addition, all other phase switches (S 1 -S 3 ) are turned ON to operate the SRM phases in freewheeling mode.

3.
If S sh is ON (non-shoot through mode), the algorithm will check the measured current of the on-going phase (k).

4.
If the current of that phase is less than its reference value, the switches (S u and S k ) are turned ON to apply positive voltage during that phase (magnetization mode). On the other hand, the switch S d , along with the switches of the other phases, is turned OFF to operate these phases in freewheeling mode.

5.
If the current of the on-going phase (k) is higher than or equal to its reference phase current, the algorithm will check the measured current of the off-going phase (k-1).

6.
If there is no current in that phase (which means that the off-going phase is completely demagnetized), then freewheeling should be applied to on-going and off-going SRM phases. There are two options to achieve this mode: the first option is to turn the switch S d ON along with all other phase switches (S 1 -S 3 ), and the second option is to turn the switch S u ON and turn OFF all other phase switches. 7.
If there is still current flowing in the off-going phase (k-1), negative voltage is applied to that phase to accelerate the demagnetization process; this is achieved through turning the switch S d ON and turning the S k-1 phase switch OFF; meanwhile, the remaining phases are operated in freewheeling mode by turning their corresponding switches ON.

Algorithm#2
1-2. The first and second steps are identical to those in algorithm#1.
3. If S sh is ON (non-shoot through mode), the algorithm will check the measured current of the off-going phase (k-1).

•
If the current of that phase is more than zero, the S d switch is turned ON to apply negative voltage to that phase (demagnetization mode). Otherwise, the other phase switches (S i(i#k-1) ) are turned ON to operate these phases in freewheeling mode.

•
If the off-going phase (k-1) is fully demagnetized, i.e., its current becomes zero, the algorithm will check the measured current of the on-going phase (k).

•
If the current of that phase is less than its reference value, the switches (S u and S k ) are turned ON to apply positive voltage during that phase (magnetization mode). On the other hand, the switch S d , along with the other phase switches, is turned OFF to operate these phases in freewheeling mode.

•
If the current of that phase is more than or equal to its reference value, the switch S d and all phase switches are turned ON to operate all the phases in freewheeling mode.

Results and Discussion
The performance of SRM with the above-introduced switching algorithms was investigated. For this purpose, the overall control system shown in Figure 6 was implemented using Matlab/Simulation. Table 1 illustrates the simulation parameters for QZIMPC and SRM. The simulation is carried out under steady-state conditions and dynamic conditions where the reference speed is stepped up. The reference value of the voltage over the capacitor C 2 is 250 V. For each algorithm, the simulation is carried out at two reference speeds of 500 rpm and 1000 rpm.  Figures 8 and 9 show the results at the reference speeds of 500 rpm, and 1000 rpm, respectively. Figures 10 and 11 show the results for algorithm#2 at the same reference speeds. According to the simulation results, Table 2 lists the peak-to-peak values of the electrical torque (∆T e ) along with the steady-state value of the SRM phase current (I ph ). The torque ripple is usually determined in terms of ∆T e as follows [21]: where T ave is the average developed electrical torque. By neglecting the mechanical losses, this average torque is equal to the load torque. Thus, at constant load torque, the value of ∆T e is usually used to imply the torque ripple [11,21].     The following points can be inferred from the simulation results: • Table 2 shows that algorithm#1 offers low torque ripple compared to the switching algorithm#2. This can be illustrated using the torque expression in (1). According to this expression, the torque is changed with the square of the phase current. Therefore, during the demagnetization period of the off-going phase, the value of the torque produced from that phase will be decreased. To maintain constant torque, current overlap between the on-going and off-going phases should be adopted. As algorithm#1 guarantees the overlap operation of the two phases, the torque ripple can be significantly reduced. On the other hand, algorithm#2 does not allow for the magnetization of the on-going phase without ensuring complete demagnetization of the off-going phase. Therefore, the developed torque will contain higher ripple during commutation.

•
There is almost no significant change in the SRM phase current between the two algorithms. It is worth noting that increasing the speed of SRM does not significantly increase the SRM phase current. Increasing the speed mainly causes an increase in the input current. This implies that the motor's increased speed is not limited by the cross-section area of the phase winding. Compared to the results revealed from [10], the switching algorithms introduced here offer wide speed range operation.

•
The capacitor voltage is well tracked. The voltage ripples over the two capacitors are also small. This guarantees the low thermal stresses expected on the capacitors of the quasi-Z-source unit. The frequency of the voltage ripples increases with motor speed. • According to the simulation results, more speed ripples can be observed at low speed using the two switching algorithms. Thus, adaptive controllers should be used for better performance over a wide speed range. Such adaptive controllers are usually used in systems with high inherent nonlinear characteristics, such as SRM. High performance can hardly be acquired over wide operating points by using traditional linear controllers, and these are generally not sufficient for high-performance drives. The literature has already proposed some adaptive methods to achieve this purpose with SRM, such as those in [22][23][24]. Figures 12 and 13 show the related waveforms under step change in the reference speed from 750 to 1000 rpm. The motor speed is successfully changed to the new speed, and the voltage values over the capacitors are also restored after this step change. This confirms the dynamic performance of the control system with the introduced switching algorithms.  From these results, it can be concluded that the switching algorithm#1 offers a better performance than algorithm#2. This is due to the availability of overlap operations between the on-going and off-going phases during the commutation period.

Conclusions
This work presents two switching algorithms intended to improve the performance of SRM driven by QZIMPC. The proposed switching algorithms are based on prioritization of the control command to fulfill the required load torque for the on-going and off-going phases, as well as to accelerate the commutation process as much as possible. These algorithms do not interfere with higher level controllers, which include speed controllers, or torque ripple minimization. The feasibility of the proposed algorithms and their effect on the performance of SRM is investigated. The simulation results show that the switching algorithm#1 offers a better performance than algorithm#2. This can be explained as follows: during the demagnetization period of the off-going phase, the value of the torque produced from that phase will be decreased. This is due to the variation between the developed phase torque and the square of the phase current. Therefore, to keep the developed torque constant, current overlap between the on-going and off-going phase should be adopted. As algorithm#1 guarantees this overlap, it can offer significant a reduction in torque ripple. Algorithm#2, on the other hand, does not allow for magnetization of the on-going phase without first ensuring complete demagnetization of the off-going phase; therefore, any torque it develops will contain higher ripple during commutation.