{'fraction_non_alphanumeric': 0.023758099352051837, 'fraction_numerical': 0.013705570221048983, 'mean_word_length': 4.736310798409299, 'pattern_counts': {'":': 0, '<': 0, '<?xml version=': 0, '>': 0, 'https://': 0, 'lorem ipsum': 0, 'www.': 0, 'xml': 0}, 'pii_count': 0, 'substrings_counts': 0, 'word_list_counts': {'cursed_substrings.json': 0, 'profanity_word_list.json': 0, 'sexual_word_list.json': 0, 'zh_pornsignals.json': 0}}
Triple-Band Implantable Antenna Design for Biotelemetry Applications in MICS/ISM/Wi-Fi/Bluetooth Bands

: Our objective is to design triple-band implantable antennas with wide bandwidths and appropriate sizes for biomedical applications. The targeted design frequencies are 400 MHz, 2.4 GHz, and the new Wi-Fi band of 5.7 GHz. Three triple-band antennas with bandwidth improvements are presented to insure all-time data connection. The proposed triple-band implantable antennas beneﬁt from combining long-distance data transfer at lower frequency bands and a higher effective bandwidth, and high-speed communications at higher frequency bands, which will have ﬂexibility for a variety of applications. A comprehensive explanation of the design procedure to achieve multiple-band implantable antennas is provided. Furthermore, miniaturization techniques are utilized to design antennas in compact sizes suitable for biomedical applications. In this paper, three-layer structures including skin, fat, and muscle are used for the designs, then antennas are placed in the chest, neck, head, and hand of different human voxels to compare antennas’ performance. Additionally, normal and overweight human effects on antenna performance were compared. Antennas have 2 to 6 dBi directivity for telemetry usage, and they are designed to satisfy the absorption limit for the human body to keep the Speciﬁc Absorption Rate (SAR) averaged over 1 g of tissue less than 1.6 W/kg and over 10 g of tissue less than 2 W/kg, according to IEEE standard. The antennas include fractal, meandered, and comb types with sizes of 1.4 mm × 10 mm × 10 mm, 3.04 mm × 10 mm × 17.25 mm, and 1.4 mm × 12 mm × 12 mm, respectively. The designed antenna showed an impedance bandwidth of 53 MHz to 120 MHz, 90 MHz to 320 MHz, and 300 MHz to 1200 MHz at the three bands. The meandered antenna was selected for validation of simulations, and its S parameters were measured in the equivalent liquid phantom of body tissues.


Introduction
In recent years, novel medical devices, such as wearables and patches, have been receiving a lot of attention in the field of biomedical research and the healthcare industry, providing solutions to a host of applications. Especially, the current global COVID-19 pandemic has led to a critical demand for person-centered healthcare instead of the conventional hospital-centered manner to reduce unnecessary contact as well as to relieve the burden on the healthcare system. The possibility of collecting vital data from a body and reprogramming in-body sets through wireless communications made implantable devices unique. Implantable antennas have been discussed since 2004, and they have reduced the need for further surgeries [1][2][3][4]. These wireless implantable products are widely used for clinical diagnosis and treatment applications, such as implantable medicine, nerve stimulation, and reprogramming of pacemakers or drug delivery, without the need for multiple surgeries [5][6][7]. To design implantable antennas, many parameters should be considered, including specific absorption rate (SAR) [8], dimension limits, biocompatibility, and sufficient bandwidth.
For the safety of the human body, the maximum power transmitted by the implantable antenna should not exceed certain levels that are imposed by regulations to avoid adverse health effects by electromagnetic emissions. For this purpose, the IEEE C95.1-1999 standard restricts specific absorption rate (SAR) averaged over 1 g of tissue to be less than 1.6 W/kg [8]. SAR is primarily dominated by electric fields in the tissue, and it is given by the following formula: developed novel triple-band antennas to take advantage of high-speed communications and long-distance data transmission together in one set. Lower frequencies are more desirable for long-distance communications since the wave propagation has less attenuation along the path and high frequencies are more suitable for high-speed communications since they provide a higher effective BW. Therefore, by designing the antennas to operate at 400 MHz from MICS band and 2.4 GHz and 5.7 GHz from ISM bands, better implantable antennas with flexibility for a variety of applications have been achieved. Furthermore, due to the popularity of the Internet of Things (IoT) in daily usage, the proposed antennas are designed at 5.7 GHz band to support both Bluetooth and Wi-Fi bands in addition to the ISM band.

Materials and Methods
Consumer electronics and communications advancements have been continuously demanding for an antenna with a more compact design, higher bandwidth, and other performance metric improvements. Numerous antenna miniaturization methods have been suggested to reduce the dimension and to enhance the bandwidth and radiation gain of the antenna. One of these techniques involves use of metamaterials in antennas. In this method, metamaterial structures made of periodic subwavelength unit cells are loaded onto the antenna [18,19]. These metamaterial structures show unique properties, such as negative permittivity or permeability, which can provide lower resonant frequency at similar antenna dimensions and hence help with antenna miniaturization and enhancement of the antenna's bandwidth and gain. Several antenna bandwidth enhancement and miniaturization based on this method have been reported and demonstrated in the literature [20,21].
Another common antenna miniaturization techniques includes introducing spacefilling curves to the antenna's structure, which is utilized in this paper to design the proposed antenna. The idea is to use the available space efficiently to fit a larger radiating structure based on special mathematical curves. With this technique, the current distribution of the antenna should be well managed to constructively add at selected frequencies and angular directions. Otherwise, the radiation characteristics of the antenna, such as impedance matching, bandwidth, and gain, will degrade by miniaturization. Fractal antennas are one of the examples in this group in which an inherent geometrical self-similarity is used to achieve space-filling structures [22]. The Antenna I design is based on fractal structures, which uses Hilbert curves. Meander antennas are another example in this miniaturization group in which the structure of the antenna is miniaturized by introducing bendings and curves to the antenna's geometry [22]. The Antenna II design is based on the meander structure. It can be seen in the Results section that meander structures are more successful in maintaining the radiation characteristics of the antenna compared to fractal antennas. Overall, adding more curves to the antenna's structure comes at the expense of reducing radiation efficiency and bandwidth because some currents in the opposite phase are usually introduced in the structure of the antenna. Hence, a novel method previously proposed in [23] for the miniaturization of dual-band antennas is used here in the design of Antenna III for the design of a triple-band antenna. It can be seen in the Results section that this design is superior to the other two designs in terms of better radiation characteristics and smaller dimensions. In the design of the antennas, the inverted F method was used for feeding the antennas and tuning the input impedance to match the coaxial cable impedance. The planar inverted F antenna (PIFA) is a quarter-wavelength patch antenna with a shorting pin at the end. Since the antenna is shorted at the end, the current at the end of the patch antenna is no longer zero, and it has a path to flow in. In the planar inverted F antenna, the feed point is placed between the open and the short ends to adjust the input impedance of the antenna, while maintaining its high radiation efficiency.

Simulation Models
Our antennas are implantable in the fat tissue of the skin. Three-layer phantoms, including skin, fat, and muscle with thicknesses of 4 mm, 4 mm, and 8 mm, were chosen for the design. For the human body model, different thicknesses have been reported in the literature depending on the body type and also different body tissues. For example, for arm and chest, skin thicknesses of 2 mm and 5 mm have been reported. Similarly, depending on the body fat index of the human body, fat thicknesses between 2 mm to 15 mm have been measured [24]. In our modeling and simulation, in order to have results applicable to a broader range of cases, we selected average values of 4 mm and 4 mm for skin and fat thicknesses. For muscles thickness, since the simulation time increases with the increase of the model volume, our simulations showed that an 8 mm thickness can be appropriately assumed for the muscle thickness. Further increasing the muscle thickness did not show any significant changes in the simulation results. Therefore, by selecting a muscle thickness of 8 mm, accurate simulation results and lower simulation time have been accomplished. EM characteristics of these tissues are dispersive and thus dispersive models of these tissues in CST were used for the simulation. The dimensions of the phantom have been optimized for reliable results, and they are approximately 5 cm × 5 cm. A superstrate is used in addition to the substrate layer to avoid contact with conductive tissues. With the proper selection of feeding points, the input impedances of all designs are 50 Ohm. The substrate and the superstrate used in this paper are Rogers 3003 and Rogers 3210, with relative permittivities of 3 and 10.2 and loss tangents of 0.0013 and 0.0027, respectively [25]. Rogers 3210 is used in the design of Antenna I and III and Rogers 3003 is used in the design of Antenna II. In all designs, the first step is specifying the path for the first resonant frequency. The second and third resonances are added by introducing extra branches. To miniaturize the antennas, all of them benefit from the PIFA idea to reduce the size to half of ordinary designs because of ground via and λ/4 length instead of λ/2. Other methods used in antenna miniaturization are introduced in the following [26][27][28]. Structures and dimensions of the three designs can be seen in Figure 1 and Table 1, and the electrical surface current distribution of each antenna can be viewed in Figure 2.

Antenna I
In this design, the first order of the Hilbert method is used to miniaturize the antenna for the first resonant frequency. By adding more vertices to the geometry of the antenna and bending the antenna's shape in a quasi-periodic pattern, we were able to miniaturize the antenna's dimensions. The effective length of the antenna does not decrease, but the required area is smaller since the length of the antenna is distributed more evenly on the surface. Then, this idea was combined with the inverted F method so that the input impedance of the antenna could be tuned for the impedance matching by moving the location of the input port and also have the effective length of the antenna λ/4. After the main body and dimensions of the antenna are determined for 400 MHz resonance frequency and the current distribution is observed by the simulation, other branches are added to the high-current nodes of the antenna to achieve the other resonant frequencies at 2.45 GHz and 5.63 GHz bands. Adding the branches to the high-current nodes also increases the capacitance between the lines, which also helps to further decrease the antenna size to 1.4 mm × 10 mm × 10 mm. branches. To miniaturize the antennas, all of them benefit from the PIFA idea to reduce the size to half of ordinary designs because of ground via and λ/4 length instead of λ/2. Other methods used in antenna miniaturization are introduced in the following [26][27][28]. Structures and dimensions of the three designs can be seen in Figure 1 and Table 1, and the electrical surface current distribution of each antenna can be viewed in Figure 2.

Antenna I
In this design, the first order of the Hilbert method is used to miniaturize the antenna for the first resonant frequency. By adding more vertices to the geometry of the antenna and bending the antenna's shape in a quasi-periodic pattern, we were able to miniaturize the antenna's dimensions. The effective length of the antenna does not decrease, but the required area is smaller since the length of the antenna is distributed more evenly on the surface. Then, this idea was combined with the inverted F method so that the input impedance of the antenna could be tuned for the impedance matching by moving the location of the input port and also have the effective length of the antenna λ/4. After the main body and dimensions of the antenna are determined for 400 MHz resonance frequency and the current distribution is observed by the simulation, other branches are added to the high-current nodes of the antenna to achieve the other resonant frequencies at 2.45

Antenna II
The structure of this antenna is based on the meander geometry. In this design, similar to the previous design, the method of adding vertices and bending points to the path of the antenna is utilized. However, there is a significant difference in the implementation of this idea compared to the previous design; in this method, periodic units with an odd number of lines are used to reduce the occupied area by the antenna. As seen in Figure 1c, each periodic cell has three current paths; two forward-going paths and one backward-going path, which practically increases the effective length of the antenna three times in the same occupied area, with a minimal negative effect on the antenna's radiation pattern and gain. This idea can be expanded to higher numbers of current paths in each periodic unit cell. However, it should be noted that the number of the current paths in each unit cell needs to be an odd number because when the forward-going and backward-going current paths with opposite directions are placed close to each other on the antenna's structure, they can cancel each other's radiation and decrease the gain. Therefore, by having an odd number of current paths in each unit cell, we will have one complete effective radiating current path, which has a minimal effect on the radiation and gain but the required area for the antenna is considerably decreased. Finally, the number of the antenna's main branches, which is also periodic, needs to be an odd number as well for similar radiation consideration. As you can see in Figure 1, the number of main branches is 5 in Antenna II and 3 in Antenna I for this reason. Furthermore, the reason that Antenna II has more major current branches compared to Antenna I is that the substrate's relative dielectric constant is 10.2 in Antenna I and 3 in Antenna II. Therefore, Antenna I needs less length to have the effective length of a quarter wavelength (λ/4) due to the higher dielectric constant of its substrate. It should also be noted that, in the design of Antenna II, having a lower substrate dielectric constant and a thicker substrate thickness can reduce the effective capacitance to the ground and consequently achieve a better radiation gain and bandwidth. At the end, similar to the previous design, after the main body and dimensions of the antenna are determined for 400 MHz resonance frequency, other branches are added to some of the high-current nodes to create quarter-wavelength current paths to obtain higher resonance frequencies at 2.4 GHZ and 5.7 GHz bands. Consequently, by using the T-shape branches, three resonant frequencies can be tuned almost independently. The inverted F method is also incorporated to tune the input impedance by changing the input port location. The use of periodic unit cells in this design helped to miniaturize the structure by approximately 40% and to reduce the dimensions of the antenna to 3.04 mm × 10 mm × 17.25 mm.

Antenna III
The miniaturization technique used for Antenna III is different from the Antenna I and II designs. In patch antennas, one effective way to reduce the antenna's area and improve the bandwidth is to introduce slots in the structure of the antenna. In this method, by having slots and defects in the antenna's shape, we can cause curves and bendings in the current paths and consequently have a smaller area, without the need to introduce vertices in the antenna's structure itself. Additionally, by adding periodic slots in Antenna III, we have periodic capacitances between the adjacent branches, which decreases the resonance frequency and hence further reduces the area of the antenna. It is also worth noting that since there is no opposite going current paths in this design, miniaturization has the least negative effect on the radiation pattern. Finally, similar to the previous designs, the inverted F method is used to tune the input impedance, and additional branches at high-current nodes are introduced to achieve resonance frequencies of 2.4 GHz and 5.7 GHz bands. This configuration has the best BW among the three designs. Unlike the other geometries, in the comb antenna, the input port is located at the beginning of the structure. The dimensions are 1.4 mm × 12 mm × 12 mm.  The step-by-step process for designing a multiple-band implantable antenna is shown in Figure 3. In the next section, the results and performance of the mentioned implantable antennas in the equivalent phantom are compared [29].

Results
The S11 of implantable antennas at the three bands are shown in Figure 4a-c, and the center resonant frequency and BWs can be obtained from diagrams, which are indicated in Table 1. Patterns of the antennas versus ϴ at three bands are also observed in Figure  4d-l, which shows a sufficient pattern suitable for implantable applications. Other characteristics are presented in the following. It can be seen that the BW of the comb antenna is more than the other designs [30][31][32]. The step-by-step process for designing a multiple-band implantable antenna is shown in Figure 3. In the next section, the results and performance of the mentioned implantable antennas in the equivalent phantom are compared [29]. The step-by-step process for designing a multiple-band implantable antenna is shown in Figure 3. In the next section, the results and performance of the mentioned implantable antennas in the equivalent phantom are compared [29].

Results
The S11 of implantable antennas at the three bands are shown in Figure 4a-c, and the center resonant frequency and BWs can be obtained from diagrams, which are indicated in Table 1. Patterns of the antennas versus ϴ at three bands are also observed in Figure  4d-l, which shows a sufficient pattern suitable for implantable applications. Other characteristics are presented in the following. It can be seen that the BW of the comb antenna is more than the other designs [30][31][32].

Results
The S 11 of implantable antennas at the three bands are shown in Figure 4a-c, and the center resonant frequency and BWs can be obtained from diagrams, which are indicated in Table 1. Patterns of the antennas versus θ at three bands are also observed in Figure 4d-l, which shows a sufficient pattern suitable for implantable applications. Other characteristics are presented in the following. It can be seen that the BW of the comb antenna is more than the other designs [30][31][32]. The step-by-step process for designing a multiple-band implantable antenna is shown in Figure 3. In the next section, the results and performance of the mentioned implantable antennas in the equivalent phantom are compared [29].

Results
The S11 of implantable antennas at the three bands are shown in Figure 4a-c, and the center resonant frequency and BWs can be obtained from diagrams, which are indicated in Table 1. Patterns of the antennas versus ϴ at three bands are also observed in Figure  4d-l, which shows a sufficient pattern suitable for implantable applications. Other characteristics are presented in the following. It can be seen that the BW of the comb antenna is more than the other designs [30][31][32].

Design Characteristics
In Table 1, the center frequencies and other characteristics of the designs as well as some reported implantable antennas are presented. It is observed that the first and the third designs are smaller in size than most of the other samples. All designs have better BW in at least 2 bands of operation in comparison with other reported samples. Among our designs, the comb antenna has the best BW, and it can be used in all new Wi-Fi bands, including indoor, outdoor, and the 5 to 6 GHz range. Since samples are dual-band implantable antennas, some cells in the SAR limit is another important criterion in implantable antennas for the safety concern of the human body. The IEEE standard [8] restricts the Specific Absorption Rate (SAR) averaged over 1 g of tissue is less than 1.6 W/kg and over 10 g of tissue is less than 2 W/kg. In our simulations, the peak SAR in 1 g of the tissue was less than 300 W/Kg for 0.5 W stimulation power in three antennas, therefore, to observe the SAR limits, the input power should not exceed 2.5 mW to preserve a SAR of less than 1.6 W/Kg. Calculated SAR from 1 w input power for all antennas are shown in Table 2

Design Characteristics
In Table 1, the center frequencies and other characteristics of the designs as well as some reported implantable antennas are presented. It is observed that the first and the third designs are smaller in size than most of the other samples. All designs have better BW in at least 2 bands of operation in comparison with other reported samples. Among our designs, the comb antenna has the best BW, and it can be used in all new Wi-Fi bands, including indoor, outdoor, and the 5 to 6 GHz range. Since samples are dual-band implantable antennas, some cells in the Table do not have entries. SAR limit is another important criterion in implantable antennas for the safety concern of the human body. The IEEE standard [8] restricts the Specific Absorption Rate (SAR) averaged over 1 g of tissue is less than 1.6 W/kg and over 10 g of tissue is less than 2 W/kg. In our simulations, the peak SAR in 1 g of the tissue was less than 300 W/Kg for 0.5 W stimulation power in three antennas, therefore, to observe the SAR limits, the input power should not exceed 2.5 mW to preserve a SAR of less than 1.6 W/Kg. Calculated SAR from 1 w input power for all antennas are shown in Table 2. Since in implantable applications, the antenna is communicating with an indoor communication point, such as Wi-Fi, this input power is sufficient for the intended biotelemetry applications and the indoor communication ranges. For example, most Wi-Fi or Bluetooth transceivers can easily communicate with signal levels of −70 dbm to −80 dbm. Assuming an input power of 2.5 mw and an average antenna gain of −15 db at 2.4 GHz frequency band, we can have up to a 10 m to 25 m distance for effective indoor communication. For 400 MHz and 5.7 GHz bands, the available distance for effective communication will be, respectively, higher and lower than the 2.4 GHz band due to the quadratic relationship between the free-space path loss and the wavelength. At 400 MHz the antenna can communicate to further distances but at a lower data rate because of lower bandwidth.

Effects of Body Tissue and Body Types
Since the comb and meander antennas showed a better performance, alteration in the performance of these antennas in different parts of the body was investigated. The percentage of the alteration of the resonant frequencies and bandwidth for the position placement of the antennas in the human voxel in comparison with the results of the antennas' simulation in the three-layer phantom model is illustrated in Figure 5. Laura human voxel of CST was selected for this simulation. Figure 5a shows four different possible placements of the implantable antennas in the body including chest, neck, arm, and head. Due to different electrical properties and the nonhomogeneity of each part of the body, some changes in the performance of each antenna are expected. Figure 5c,d demonstrate the box plots of the variations in the resonant frequency and bandwidth of the comb and meander antennas at the three bands, when placed in the chest, neck, arm, and hand. The minimum, first quartile, median, third quartile, and maximum of the variations are presented in these figures. Based on the results in the human voxel, the meander antenna has a more stable performance at 400 MHZ band and the comb antenna has a better performance stability in 2.4 GHz and 5.7 GHz bands due to the implant location in the body. Both antennas have acceptable alterations as the operational frequency bands are covered in all simulations even in the head placement, which has thinner skin and considerably more skull tissue. The results also show that the bandwidth at 400 MHz and 2.4 GHz bands became slightly narrower and slightly wider in the 5.7 GHz band in the voxel in comparison to the three-layer phantom model.
To compare the effect of different human body types on the antennas' performance, an overweight body model with a greater body fat index was selected, and it is shown in Figure 6. The percentage of the performance variation in both resonant frequency and bandwidth of the meander antenna in the neck and hand of the human voxel are presented. Results show that the resonant frequency and bandwidth are reduced in an overweight voxel in 400 MHZ, but it does not follow an arranged variation pattern at 2.4 GHz and 5.7 GHz bands, although the operational frequency bands are still covered in the overweight voxel similar to the normal voxel.
Technologies 2022, 10, x FOR PEER REVIEW 11 of 17 the available distance for effective communication will be, respectively, higher and lower than the 2.4 GHz band due to the quadratic relationship between the free-space path loss and the wavelength. At 400 MHz the antenna can communicate to further distances but at a lower data rate because of lower bandwidth.

Effects of Body Tissue and Body Types
Since the comb and meander antennas showed a better performance, alteration in the performance of these antennas in different parts of the body was investigated. The percentage of the alteration of the resonant frequencies and bandwidth for the position placement of the antennas in the human voxel in comparison with the results of the antennas' simulation in the three-layer phantom model is illustrated in Figure 5. Laura human voxel of CST was selected for this simulation. Figure 5a shows four different possible placements of the implantable antennas in the body including chest, neck, arm, and head. Due to different electrical properties and the nonhomogeneity of each part of the body, some changes in the performance of each antenna are expected. Figure 5c,d demonstrate the box plots of the variations in the resonant frequency and bandwidth of the comb and meander antennas at the three bands, when placed in the chest, neck, arm, and hand. The minimum, first quartile, median, third quartile, and maximum of the variations are presented in these figures. Based on the results in the human voxel, the meander antenna has a more stable performance at 400 MHZ band and the comb antenna has a better performance stability in 2.4 GHz and 5.7 GHz bands due to the implant location in the body. Both antennas have acceptable alterations as the operational frequency bands are covered in all simulations even in the head placement, which has thinner skin and considerably more skull tissue. The results also show that the bandwidth at 400 MHz and 2.4 GHz bands became slightly narrower and slightly wider in the 5.7 GHz band in the voxel in comparison to the three-layer phantom model. To compare the effect of different human body types on the antennas' performance, an overweight body model with a greater body fat index was selected, and it is shown in Figure 6. The percentage of the performance variation in both resonant frequency and bandwidth of the meander antenna in the neck and hand of the human voxel are presented. Results show that the resonant frequency and bandwidth are reduced in an overweight voxel in 400 MHZ, but it does not follow an arranged variation pattern at 2.4 GHz and 5.7 GHz bands, although the operational frequency bands are still covered in the overweight voxel similar to the normal voxel.  To compare the effect of different human body types on the antennas' performance, an overweight body model with a greater body fat index was selected, and it is shown in Figure 6. The percentage of the performance variation in both resonant frequency and bandwidth of the meander antenna in the neck and hand of the human voxel are presented. Results show that the resonant frequency and bandwidth are reduced in an overweight voxel in 400 MHZ, but it does not follow an arranged variation pattern at 2.4 GHz and 5.7 GHz bands, although the operational frequency bands are still covered in the overweight voxel similar to the normal voxel.

Mesaurements
Due to less stringent fabrication requirements for the meandered antenna (Antenna II), it was selected as a sample for fabrication and validation of the simulation results. The fabricated structure of antenna II with and without the superstrate is shown in Figure 7a.

Mesaurements
Due to less stringent fabrication requirements for the meandered antenna (Antenna II), it was selected as a sample for fabrication and validation of the simulation results. The fabricated structure of antenna II with and without the superstrate is shown in Figure 7a.

Mesaurements
Due to less stringent fabrication requirements for the meandered antenna (Antenna II), it was selected as a sample for fabrication and validation of the simulation results. The fabricated structure of antenna II with and without the superstrate is shown in Figure 7a. Mixtures of n-butanol, propanol, salt, and purified water with TDS = 5, at different concentrations, were prepared and measured by an open-ended coaxial line [39,40] to make sure the effective EM characteristics of the equivalent three-layer phantom in each frequency band are in good agreement with that of the human tissues (skin, fat, and muscle). The percentage of each material is illustrated in Table 3 in each frequency [41,42]. The results are shown versus the frequency at each band in Figure 7b-d. The S 11 measurement results are illustrated in Figure 8a-c. The results show a good agreement in the first two bands, between test results and the simulation results of the threelayer mode, but some discrepancies are observed in the third frequency band. The reasons are the nonideal behavior of the connectors, ports, and coaxial cables at 5.7 GHz. The coaxial cable connection to the antenna was done by hand, and this creates impedance mismatches since the input impedance becomes more sensitive to the location of the feeding point as the frequency increases. Furthermore, the need for a thin protective layer on the antenna (with a relative permittivity of approximately 3) to avoid penetration of the liquid to the substrate and replacing a one-layer liquid phantom instead of the three-layer phantom in the measurement are the other reasons for the small differences between simulations and measurement results.
concentrations, were prepared and measured by an open-ended coaxial line [39,40] to make sure the effective EM characteristics of the equivalent three-layer phantom in each frequency band are in good agreement with that of the human tissues (skin, fat, and muscle). The percentage of each material is illustrated in Table 3 in each frequency [41,42]. The results are shown versus the frequency at each band in Figure 7b-d. The S11 measurement results are illustrated in Figure 8a-c. The results show a good agreement in the first two bands, between test results and the simulation results of the three-layer mode, but some discrepancies are observed in the third frequency band. The reasons are the nonideal behavior of the connectors, ports, and coaxial cables at 5.7 GHz. The coaxial cable connection to the antenna was done by hand, and this creates impedance mismatches since the input impedance becomes more sensitive to the location of the feeding point as the frequency increases. Furthermore, the need for a thin protective layer on the antenna (with a relative permittivity of approximately 3) to avoid penetration of the liquid to the substrate and replacing a one-layer liquid phantom instead of the three-layer phantom in the measurement are the other reasons for the small differences between simulations and measurement results.
In order to show the effect of the thin protective coating layer and the use of onelayer liquid phantom in the measurement compared to the real three-layer phantom in the simulation, simulation results of the one-layer equivalent phantom with a coating layer are also shown along with the measurement results and the original simulation of the three-layer model with no coating in Figure 8. As expected, the use of a one-layer equivalent phantom with the coating results in a resonance frequency shift to a lower value, and it explains the small discrepancy observed between the measurement results and simulation of the three-layer model with no coating observed in Figure 8b,c. It should also be noted that the effect of the use of a one-layer equivalent phantom with a coating layer is less as frequency decreases, and it is negligible at the 400 MHz band.

Discussion and Conclusions
Implantable devices have been playing a critical role in the field of biomedical research and health monitoring. Implantable antennas can support the collection of vital data from a body and reprogramming in-body sets through wireless communications, which can be used in a variety of medical applications, such as heart signal/beat analysis, In order to show the effect of the thin protective coating layer and the use of onelayer liquid phantom in the measurement compared to the real three-layer phantom in the simulation, simulation results of the one-layer equivalent phantom with a coating layer are also shown along with the measurement results and the original simulation of the three-layer model with no coating in Figure 8. As expected, the use of a one-layer equivalent phantom with the coating results in a resonance frequency shift to a lower value, and it explains the small discrepancy observed between the measurement results and simulation of the three-layer model with no coating observed in Figure 8b,c. It should also be noted that the effect of the use of a one-layer equivalent phantom with a coating layer is less as frequency decreases, and it is negligible at the 400 MHz band.

Discussion and Conclusions
Implantable devices have been playing a critical role in the field of biomedical research and health monitoring. Implantable antennas can support the collection of vital data from a body and reprogramming in-body sets through wireless communications, which can be used in a variety of medical applications, such as heart signal/beat analysis, reprogramming of pacemakers, daily activity recording, skeletal issues and diseases diagnosis, implantable medicine, nerve stimulation, and drug delivery without the need for multiple surgeries.
The resonance frequency of antennas implanted in various people may change and alter the antenna's impedance matching because the characteristics of human tissues differ from individual to individual. In order to solve this problem, implantable antennas should have a broader bandwidth (BW). Additionally, miniaturization methods are needed to design compact implantable antennas that are compatible for biomedical purposes. Therefore, here, three triple-band implantable antennas with wide bandwidth characteristics and appropriate sizes were designed, analyzed, and compared. These antennas include fractal, meandered, and comb antennas. The antennas operate at three bands: 400 MHz, 2.4 GHz, and 5.7 GHz. The sizes of all antennas are optimized to be implanted, and they are smaller or comparable with similar reported samples. It is also notable that other recent works include only single-or dual-band antennas, and triple-band implantable antennas have rarely been reported in the literature. The BWs of all three presented designs are more than the other reported works. The comb antenna has the best BW among others. Since wider BW is more desirable in case of tissue characteristics variations, the comb antenna is more preferable in our designs. Rogers 3210 was chosen as the substrate and we obtained 120, 320, and 1200 MHz bandwidths at the specified resonant frequencies. The antenna dimensions are 1.4 mm×12 mm × 12 mm. The fractal type antenna is slightly smaller in size among the designs.
To study the performance of the antenna implanted in different body tissues and body types, antennas were placed in different body parts of the human voxels and based on our analysis in all placements operational bands were covered. In human voxel, meander antennas had a better performance stability at 400 MHZ band and comb antenna showed a better performance stability at 2.4 GHz and 5.7 GHz. The meander antenna was selected because of the ease of fabrication for validation and a liquid phantom was provided to measure the S 11 of the antenna. The antenna satisfied the SAR limit and the data connectivity requirement. The measurement results were compared to simulations and good agreement was observed.