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Switching function parameter variation analysis of a quasi- sliding mode controlled induction motor drive

Received Sep 20, 2021 Revised Feb 23, 2022 Accepted Mar 16, 2022 Sliding mode control is a nonlinear, robust control that is having better load disturbance rejection capability, less parameter sensitivity and fast dynamic response. Conventional sliding mode control introduces high chattering that can degrade the induction motor (IM) drive system responses. Hence, a quasi-sliding mode controller (Q-SMC) using a hyperbolic tangent function coupled with equivalent control is designed for robust speed control of vector-controlled IM drive in this work. This work focuses on the effect of variation of the switching function parameters of the Q-SMC on the performance of the drive. Extensive simulations are performed using MATLAB/Simulink software, and the switching function parameters are adjusted across a wide range and its impact on motor performance is studied qualitatively and quantitatively, with accompanying graphical results and various transient parameters. It is observed that a Q-SMC controller with a larger boundary layer width has less overshoot, less steady-state error, and a lower current THD. It is also observed that even though a high gain Q-SMC controller responds quickly, the percentage overshoot for high gain systems is likewise large. Hence, if the boundary layer width and switching gain parameters are optimized, a Q-SMC speed controller is a promising choice for a high-performance IM drive.


INTRODUCTION
Advances in power electronics, microcontrollers, processor-based systems, and nonlinear control theory have facilitated substantial research into advanced control approaches for induction motor (IM) drives during the last few decades. Despite the fact that induction motors are extremely complex, nonlinear, and tightly coupled [1], numerous researchers have developed various strategies for its dynamic control without compromising performance. Model predictive control (MPC) [2], Field oriented control (FOC), direct torque control (DTC) [3], feedback linearization (FL) [4] and observer-based nonlinear controllers [5] have all been presented in the literature to achieve quick dynamic responses in IM. Various sophisticated speed control approaches such as robust control, optimal control, adaptive control [6], sliding mode control (SMC) [7], and intelligent control techniques like fuzzy logic control [8], [9] and artificial neural network (ANN) are also being developed.
In this work, an indirect field-oriented control (IFOC) or indirect vector control (IVC) is applied to the IM drive. There are two control loops in vector control. The inner loop controls current, whereas the outer loop controls speed [10]. Hysteresis controller is used in the inner current loop. Classical fixed gain proportional-integral (PI) controller based IFOC drives fail to provide the desired performance when load perturbations, parametric variations [11], external disturbances or modelling uncertainties [12] are there, making the torque sluggish and oscillatory [13], which may become critical in certain applications. To address this application-oriented challenge a sliding mode controller is proposed as the speed controller in this work.
Sliding mode control is a type of nonlinear control that has two design modes: i) sliding surface design and ii) sliding mode controller design. The sliding surface has to ensure the desired transient and steady-state behaviours in it, while the controller has to accelerate the system trajectory to reach the sliding surface asymptotically or in finite time [14], [15] and to remain there afterwards, eventually attaining exact tracking asymptotically or in finite time [16]. Conventional SMC utilizes a simple sign function for switching, resulting in high-frequency chattering in the control output [17]. Control of the direct current regulated IM drive is done using conventional SMC and boundary SMC using a saturation function in [18]. Nguyen et al. [19] discusses the sliding mode control of a stator-flux-oriented three-phase IM. SMC with a fuzzy mutual reference adaptive system observer is used to estimate the speed of an IM drive in [20].
A quasi-sliding mode controller (Q-SMC) with a smooth hyperbolic tangent function is proposed in this work as the speed controller in order to reduce the chattering issue of conventional SMC and is applied in an indirect rotor field-oriented control (IRFOC) scheme. As the parameters of the switching function are varied, the performance of the induction motor will be affected. This work focus to investigate on the effect of variation of these switching function parameters on the performance of the drive. The major contributions of this work include the design of indirect rotor field-oriented control scheme of IM drive, design of a chatter-free quasi-sliding mode control using a hyperbolic tangent function coupled with equivalent control, performance comparison of Q-SMC with conventional SMC and qualitative and quantitative analysis of the impact of Q-SMC switching function parameter variation on motor performance. This paper is organized as: section 2 presents the mathematical formulation of the sliding mode control system in the IFOC induction motor drive system. Section 3 introduces the design of the Q-SMC with a hyperbolic tangent switching function. The results and discussion are given in section 4 and the conclusion in section 5.

SLIDING MODE SPEED CONTROL IN IFOC INDUCTION MOTOR DRIVE
The sliding mode speed control approach for vector-controlled induction motors is covered in this section. Here, the rotor flux angle is obtained indirectly from the slip angle speed ωsl. A sliding mode controller is used as the speed controller.

IFOC induction motor drive
The block diagram of the induction motor drive based on the indirect vector control strategy is shown in Figure 1. Decoupling between the motor flux and torque is obtained by choosing a synchronously rotating reference frame to model the induction motor and by aligning it in the direction of rotor flux. A hysteresis current controller is employed to generate gate pulses to the 2-level inverter. The currents iqs and ids are found from the d-q transformation of sensed stator currents ia, ib and ic using clarke's and park's transformations. The q-axis component of current iqs is responsible for the production of torque and the d-axis component ids for the flux. Rotor speed is measured by the encoder and these inputs are used to estimate the rotor flux (r) and slip speed (sl) in a feed-forward manner [9]. Flux rotor position (θe) obtained is necessary for d-q to a-b-c and a-b-c to d-q transformations. The actual speed measured is compared with the command speed and speed error is used for generating the sliding surface in SMC and the SMC output is the reference torque component of current (iqs * ). The reference flux component of current (ids * ) deduced from the desired rotor flux is keyed into the controller. Reference ids * and iqs * are converted to ia * , ib * and ic * and the hysteresis current controller generates the switching pulses according to the sensed stator current ia, ib and ic [21]. The power circuit consists of a DC supply and a two-level IGBT inverter feeding the three-phase induction motor.
As = 0, in rotor field oriented control [22]. Here, P represents the number of poles, Lm represents magnetizing inductance, Lr represents the self-inductance of the rotor, ψdr and ψqr represent rotor d-q-axes flux linkages. i.e., = ⅆ * is the command rotor flux. The governing equation of the motor shaft and the load dynamics is given by [16], where J represents inertia (kg-m 2 ) and ωm mechanical speed of the rotor (rad/s). Te, TL represents electromagnetic and mechanical or load torque (N.m.) while B represents the frictional coefficient (Nm.S).

Sliding mode control
Using the equivalent control approach, a sliding mode control system can be written in general as [22], Where ( ) is the control signal input and ( ) is the system output. As per the equivalent control technique, the control signal ( ) can be stated as [23], Where is the equivalent control action in charge of ensuring system convergence and is the switching control action in charge of ensuring that the sliding surface is drawn to the system state space. The controller task is to make the motor run at a speed ωm that correctly track the command speed ωref even in the occurrence of model imperfections, load torque disturbances and measurement noise.

Equivalent control
Taking into account the parametric fluctuations, external disturbances and uncertainties, as well as the unmodeled dynamics for the actual induction motor drive, dynamic in (7) can be rewritten as [13], where L(t ) represents the lumped uncertainty parameter [24], and it can be written as, and the terms  ,  and  represent the uncertainties associated with the respective terms [25]. The speed error can be stated as, where, ( ) is the speed reference and ( ) is the actual rotor speed. From (11) and (13),

Sliding surface
The sliding plane S is designed as a function of the speed error e(t), its integral ∫ . , and its derivative ( ) and can be written as, Where  1 and  2 are positive real surface parameters and these gain parameters define the slope of the sliding manifold. The convergence of this set of equations can be demonstrated using the lyapunov energy function V [23], [26].

Switching function and switching control
In conventional SMC, the switching function used is the sign function which is defined as [27], the switching control component is given by [5], where  is the sliding coefficient.
As the uncertainty bound is difficult to estimate in practice, this coefficient must be set to a large enough value so as to overcome the effect of any external disturbance [27]. This conventional SMC is very simple, but it causes high chattering because of the discontinuous nature of its switching function. Chattering is highly undesirable as it causes excessive control activity, increased power consumption and increased torque ripples [26] and thereby causes the deterioration of overall system performance in IM drives. Hence in this work, a quasi sliding mode control (Q-SMC) using a continuous hyperbolic tangent (tanh) function [28], [29] is used which is discussed in section 3.

QUASI-SLIDING MODE SPEED CONTROL
To deal with the high-frequency chattering issue, quasi-sliding mode controller (Q-SMC) is proposed that will make the state stay in a certain range at boundary layer neighbourhood. Specifically, a continuous hyperbolic tangent (tanh) function is proposed in this work instead of the discontinuous signum function. Even with nonlinear control input, the chaos linked with a motor subjected to unmatched uncertainty can be effectively suppressed or driven to a predictable and controlled bound using a quasisliding mode control (Q-SMC) approach.

Switching function
The hyperbolic tangent function is given by (20) and is shown in Figure 2.
Where  is the boundary layer width and it determines the steepness or inclination of the tanh function (>0).
As the value of  is close to zero, the switching function will approximate the sign function. The switching control component is given by, The switching gain is the output saturation value of the controller. Switching gain is employed in sliding mode as the upper bound of uncertainties. The hyperbolic tangent function is a good choice for the noisy IM control system as it is having a smoother behaviour near saturation.

Switching function parameters
The two parameters of the adopted hyperbolic tangent switching function are the switching gain and the boundary layer width . The effect of variation of these two parameters on the performance of the IM drive is investigated in Section 4. The transient parameters are also analyzed and discussed in the next section.

RESULTS AND DISCUSSION
The quasi-sliding mode speed controller based on tanh function discussed in the previous section is developed in MATLAB/ Simulink software for a 10HP IFOC induction motor drive and the effect of variation of the switching parameters and  on the performance of the motor are investigated separately in this section. The hysteresis band h taken is 0.05. The nominal value of flux, ref is taken as 0.8 pu. Table 1 shows the specifications of the squirrel cage induction motor under investigation.  Figure 3 depicts the speed response of a traditional SMC controller with a sign switching function and a Q-SMC controller with a tanh switching function when subjected to a reference speed of 1440 rpm. It is observed from the graph that the conventional SMC produces a lot of chattering whereas the oscillations in the Q-SMC speed response die out very quickly. Also, the percentage of overshoot and undershoot are high in conventional SMC compared to Q-SMC.

Case 1: variation in epsilon ( ) parameter of Q-SMC 4.2.1. Under no load and a command speed of 1440RPM
In this investigation, a command speed of 1440RPM is applied to the indirect vector-controlled IM drive under no-load condition and is simulated for 1.0S duration. The switching gain is set as 100. The simulation study is carried out with epsilon () values of 0.1, 1 and 10 and corresponding graphs are plotted below. The zoomed-in view of transient speed response from 0.12S to 0.18S with the three epsilon values is shown in Figure 4. It is evident from the graph that the Q-SMC with lower epsilon () value is having greater overshoot and high chattering.
The steady-state current graph corresponding to epsilon () values 0.1, 1 and 10 from 0.9S to 1S are shown in Figure 5. The switching gain is maintained as 100 itself. Corresponding torque responses are plotted in Figure 6. The chattering is high for epsilon () value 0.1 as observed from Figure 5 and Figure 6.

Under full load and a command speed of 1440RPM:
The simulation experiment is repeated for Full load torque at a command speed of 1440RPM and with 100. The corresponding speed responses are shown in Figure 7. The stator current Ia for different epsilon () values are shown in Figure 8 and the torque responses in Figure 9. Here, all the three response graphs reveal that the Q-SMC with lower epsilon () value is having greater overshoot and high chattering under loaded conditions also. The sliding surface S for =100 and for different epsilon () values are shown in Figure 10. The zoomed-in view is shown as a subplot in Figure 10 for a better understanding. The figure shows that the sliding surface follows the same path and very quickly reaches zero and afterwards maintain the state due to the controller action in all three cases. For a higher value of epsilon (), the sliding surface is not confining to exactly zero.

Transient performance analysis:
The transient performance analysis with the different epsilon () values are carried out in simulation for Q-SMC for a command speed of 1440RPM and for no-load and full load condition and is recorded in Table 2. It can be found that the controller with lower epsilon () value gives higher overshoot, higher steady-  Table 2. It can be concluded that the larger the width of the boundary layer, the smoother the control signal [30]. Even though the boundary layer design is intended to reduce chattering, it does not drive the system state to the origin but instead has a small residual set around the origin. That is, a wide boundary layer width is preferable for control signal smoothness, whereas a small boundary layer width is chosen for control accuracy. Hence an optimum value of boundary layer width should be selected for better performance.

Case 2: variation in switching gain ( )of Q-SMC: 4.3.1. Under no load and a command speed of 1/3 rd rated speed (480RPM) with epsilon () = 1
In this study, a command speed of 1/3 rd rated speed (480RPM) is applied to the IM drive under the no-load condition with boundary layer width  set as 1 and is simulated for 1.0S duration. The simulation work is carried out with a switching gain of 50, 100 and 150 respectively. Corresponding graphs are plotted with all the three values. Figure 11 shows the reference speed and actual speed response obtained with the three switching gain values. The zoomed-in view of transient speed response from 0.04S to 0.14S is given as a subplot in it. It can be observed from the plot that, as the gain ( ) is reduced, predominant oscillations in the speed graph are reduced and response becomes slower. The controller with value 50 took a much higher time to reach its peak than the system with value 150. Also, the higher the gain, the greater the percentage overshoot. The corresponding stator current graphs are shown in Figure 12 and the torque responses in Figure 13.  Figure 15. Here, all the three response graphs reveal that the Q-SMC with higher Gain ( ) is having a fast dynamic response, large overshoot and high oscillations under loaded conditions also. The sliding surface s for =1 and for different gain ( ) values are plotted in Figure 16. It shows that the sliding surface S takes different paths to reach the sliding manifold S=0 as the gain parameter is varied and afterwards maintain the state due to the controller action in all the three cases with different gain ( ) values.

Transient performance analysis
The transient performance analysis with the different switching gain ( ) values are carried out in simulation for Q-SMC for a command speed of 480RPM and a load torque of 0 Nm (No Load) and 24.75 Nm (Half Load) and is recorded in Table 3. By analysing the Table data, we can conclude that rise time, settling time, peak time and steady-state error are higher for systems with lower gain ( ) values under no-load and loaded conditions. That means the Q-SMC with higher switching gain responds quickly. Even though the dynamic response of high gain systems is fast, the percentage overshoot is also high for high gain systems and it is to be limited in IM drive applications. The current THD value is more or less the same in all systems with different switching gain ( ) values as compared to case 1.
So, it can be concluded that the magnitude of chattering is proportional to switching gain which represents the upper bound of uncertainties of the system. If this upper bound selected is too large, the switching control law will result in a serious chattering phenomenon. Contrarily, if the bound selected is too small, the stability conditions may not be met. Hence, an adequate switching gain value should be chosen to decrease the amplitude of chattering at the same time preserving the existence of sliding mode control.

CONCLUSION
In this paper, the design of a quasi-sliding mode speed controller for the IM drive is presented with hysteresis current controller. The indirect vector control technique and the quasi-sliding mode speed controller as applied to an induction motor drive is discussed. The signum switching function of conventional SMC is replaced by the hyperbolic tangent function to make it a smooth function instead of a discontinuous function. In this work, the boundary layer width  and the switching gain of the tanh function are varied across a range of 0.01 to 10 and 50 to 150 respectively and its effect on the IM drive performance is investigated both qualitatively and quantitatively. Extensive simulations are carried out with applied switching function parameter variations and the resulting impacts on the drive performance are analysed graphically. Transient analysis parameters and current THD are also tabulated that represent a quantitative measure of the effect of variation of switching function parameters on drive performance. A boundary layer width that is too small results in significant overshoot and chattering. Choice of boundary layer width is a trade-off between smoothness of the control signal and control accuracy. High value of switching gain results in high overshoot and chattering in spite of a fast stabilized system response. Hence a Q-SMC with an optimum value of boundary layer width and switching gain parameter results in enhanced performance of the IM drive.